ADE7953

2022-07-21 来源：客趣旅游网

Single Phase, Multifunction Metering IC

with Neutral Current Measurement

ADE7953

The device incorporates three Σ-Δ ADCs with a high accuracy energy measurement core. The second input channel simulta-neously measures neutral current and enables tamper detection and neutral current billing. The additional channel incorporates a complete signal path that allows a full range of measurements. Each input channel supports independent and flexible gain stages, making the device suitable for use with a variety of current sensors such as current transformers (CTs) and low value shunt resistors. Two on-chip integrators facilitate the use of Rogowski coil sensors. The ADE7953 provides access to on-chip meter registers via a variety of communication interfaces including SPI, I2C, and UART. Two configurable low jitter pulse output pins provide outputs that are proportional to active, reactive, or apparent energy, as well as current and voltage rms. A full range of power quality information such as overcurrent, overvoltage, peak, and sag detection are accessible via the external IRQ pin. Independent active, reactive, and apparent no-load detections are included to prevent “meter creep.” Dedicated reverse power (REVP), zero-crossing voltage (ZX), and zero-crossing current (ZX_I) pins are also provided. The ADE7953 energy metering IC operates from a 3.3 V supply voltage and is available in a 28-lead LFCSP package.

FEATURES

Measures active, reactive, and apparent energy; sampled waveform; current and voltage rms

Provides a second current input for neutral current measurement

Less than 0.1% error in active and reactive energy measurements over a dynamic range of 3000:1

Less than 0.2% error in instantaneous IRMS measurement over a dynamic range of 1000:1

Provides apparent energy measurement and instantaneous power readings

1.23 kHz bandwidth operation Flexible PGA gain stage (up to ×22)

Includes internal integrators for use with Rogowski coil sensors SPI, I2C, or UART communication

GENERAL DESCRIPTION

The ADE7953 is a high accuracy electrical energy measurement IC intended for single phase applications. It measures line voltage and current and calculates active, reactive, and apparent energy, as well as instantaneous rms voltage and current.

FUNCTIONAL BLOCK DIAGRAM

REFLOW NOISEPRE-AMPIAPIANVPVNIBPIBNCONFIGURATIONAND CONTROLPGAADCPGAADCDSPPGAADCSINCANDDECIMATIONFILTERENERGYMETERINGPROCESSORRESETVDDVINTAVINTD1.2V REFADE7953WAVEFORMSAMPLINGREVPZXZX_IPEAKANGLEPOWERFACTORSAGAWATTAVARAVABWATTBVARBVAREVPZXZX_IAGNDDGNDUARTSPI INTERFACEI2CAENERGYARENERGYAAENERGYBRENERGYBAPENERGYAAPENERGYBDIGITALFREQUENCYCONVERSIONCF1DENCF2DENCF1CF209320-001IRQCSMISO/SDA/TxMOSI/SCL/RxSCLKCLKINCLKOUT

Figure 1.

Rev. 0

Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners.

ADE7953

Period Measurement ...................................................................... 35 Instantaneous Powers and Waveform Sampling ........................ 36 Power Factor.................................................................................... 37 Using the Line Cycle Accumulation Mode to Determine

the Power Factor ......................................................................... 37 Power Factor with No-Load Detection ................................... 37 Angle Measurement ................................................................... 38 No-Load Detection ........................................................................ 39 Setting the No-Load Thresholds .............................................. 39 Active Energy No-Load Detection ........................................... 39 Reactive Energy No-Load Detection ....................................... 40 Apparent Energy No-Load Detection ..................................... 40 Zero-Crossing Detection ............................................................... 42 Zero-Crossing Output Pins ....................................................... 42 Zero-Crossing Interrupts .......................................................... 42 Zero-Crossing Timeout ............................................................. 43 Zero-Crossing Threshold .......................................................... 43 Voltage Sag Detection .................................................................... 44 Setting the SAGCYC Register ................................................... 44 Setting the SAGLVL Register .................................................... 44 Voltage Sag Interrupt ................................................................. 44 Peak Detection ................................................................................ 45 Indication of Power Direction ...................................................... 46 Reverse Power ............................................................................. 46 Sign Indication ............................................................................ 46 Overcurrent and Overvoltage Detection..................................... 47 Setting the OVLVL and OILVL Registers ............................... 47 Overvoltage and Overcurrent Interrupts ................................ 47 Alternative Output Functions ....................................................... 48 ADE7953 Interrupts ....................................................................... 49 Primary Interrupts (Voltage Channel and Current

Channel A) .................................................................................. 49 Current Channel B Interrupts .................................................. 49 Communicating with the ADE7953 ............................................ 50 Communication Autodetection ............................................... 50 Locking the Communication Interface ................................... 50 SPI Interface ................................................................................ 51 I2C Interface ................................................................................ 52 UART Interface ........................................................................... 54

Rev. 0 | Page 2 of 68

TABLE OF CONTENTS

Features .............................................................................................. 1 General Description ......................................................................... 1 Functional Block Diagram .............................................................. 1 Revision History ............................................................................... 3 Specifications ..................................................................................... 4 Timing Characteristics ................................................................ 6 Absolute Maximum Ratings ............................................................ 8 ESD Caution .................................................................................. 8 Pin Configuration and Function Descriptions ............................. 9 Typical Performance Characteristics ........................................... 11 Test Circuit ...................................................................................... 16 Terminology .................................................................................... 17 Theory of Operation ...................................................................... 18 Analog Inputs .............................................................................. 18 Analog-to-Digital Conversion .................................................. 18 Current Channel ADCs ............................................................. 20 Voltage Channel ADC ............................................................... 21 Reference Circuit ........................................................................ 21 Root Mean Square Measurement ................................................. 22 Current Channel RMS Calculation .......................................... 22 Voltage Channel RMS Calculation ........................................... 22 Active Power Calculation .............................................................. 23 Sign of Active Power Calculation ............................................. 23 Active Energy Calculation ......................................................... 24 Active Energy Accumulation Modes ....................................... 26 Reactive Power Calculation ........................................................... 27 Sign of Reactive Power Calculation ......................................... 27 Reactive Energy Calculation ..................................................... 28 Reactive Energy Accumulation Modes ................................... 29 Apparent Power Calculation ......................................................... 30 Apparent Energy Calculation ................................................... 30 Ampere-Hour Accumulation.................................................... 31 Energy-to-Frequency Conversion ................................................ 32 Pulse Output Characteristics .................................................... 32 Energy Calibration ......................................................................... 33 Gain Calibration ......................................................................... 33 Phase Calibration ....................................................................... 33 Offset Calibration ....................................................................... 34

ADE7953

ADE7953 Registers ......................................................................... 58 ADE7953 Register Descriptions ............................................... 60 Outline Dimensions ........................................................................ 65 Ordering Guide ........................................................................... 65

Write Protection .......................................................................... 56 Communication Verification ..................................................... 56 Checksum Register ..................................................................... 57

Communication Verification and Security .................................. 56

REVISION HISTORY

2/11—Revision 0: Initial Version

Rev. 0 | Page 3 of 68

ADE7953

SPECIFICATIONS

VDD = 3.3 V ± 10%, AGND = DGND = 0 V, on-chip reference, CLKIN = 3.58 MHz, TMIN to TMAX = −40°C to +85°C, unless otherwise noted. Table 1.

Parameter in Typ ax Unit Test Conditions/Comments

PHASE ERROR BETWEEN CHANNELS Line frequency = 45 Hz to 65 Hz, HPF on Power Factor = 0.8 Capacitive ±0.05 Degrees Phase lead 37° GPower Factor = 0.5 Inductive ±0.05 Degrees Phase lag 60° ACTIVE ENERY MEASUREMENT 0.1 % Active Energy Measurement Error Over a dynamic range of 3000:1, PGA = 1,

(Current Channel A) PGA = 22, integrator off

0.1 % Active Energy Measurement Error Over a dynamic range of 1000:1, PGA = 1,

(Current Channel B) PGA = 16, integrator off AC Power Supply Rejection VDD = 3.3 V ± 120 mV rms, 100 Hz Output Frequency Variation 0.01 % DC Power Supply Rejection VDD = 3.3 V ± 330 mV dc Output Frequency Variation 0.01 % Active Energy Measurement Bandwidth 1.23 kHz REACTIVE ENERY MEASUREMENT G

0.1 % Reactive Energy Measurement Error Over a dynamic range of 3000:1, PGA = 1,

(Current Channel A) PGA = 22, integrator off

0.1 % Reactive Energy Measurement Error Over a dynamic range of 1000:1, PGA = 1,

(Current Channel B) PGA = 16, integrator off AC Power Supply Rejection VDD = 3.3 V ± 120 mV rms, 100 Hz Output Frequency Variation 0.01 % DC Power Supply Rejection VDD = 3.3 V ± 330 mV dc G

Output Frequency Variation 0.01 %

1.23 kHz Reactive Energy Measurement

Bandwidth MMRMS MEASUREMENT 1.23 kHz IRMS and VRMS Measurement

Bandwidth

% IRMS (Current Channel A) Measurement 0.2 Over a dynamic range of 1000:1, PGA = 1,

Error PGA = 22, integrator off

0.2 % IRMS (Current Channel B) and VRMS Over a dynamic range of 500:1, PGA = 1,

Measurement Error PGA = 16, integrator off ANALO INPUTS Maximum Signal Levels ±500 mV peak Differential inputs: IAP to IAN, IBP to IBN ±500 mV peak Single-ended input: VP to VN, IBP to IBN ±250 mV peak Single-ended input: IAP to IAN Input Impedance (DC) IAP Pin 130 MΩ IAN Pin 70 MΩ IBP, IBN, VP, VN Pins 660 kΩ ADC Offset Error Uncalibrated error (see the Terminology section)

Current Channel B, Voltage Channel 0 mV Current Channel A −12 mV PGA = 1 −0.3 mV PGA = 16, PGA = 22 ain Error External 1.2 V reference Current Channel A ±3 % Current Channel B ±3 % Voltage Channel ±3 %

Rev. 0 | Page 4 of 68

ADE7953

Parameter in Typ ax Unit Test Conditions/Comments ANALO PERFORMANCE Signal-to-Noise Ratio Current Channel A 74 dB Current Channel B, Voltage Channel 71 dB Signal-to-Noise-and-Distortion Ratio Current Channel A, Current Channel B 68 dB Voltage Channel 65 dB Bandwidth (−3 dB) 1.23 kHz CF1 AND CF2 PULSE OUTPUTS Maximum Output Frequency 210 kHz Duty Cycle 50 % CF1 or CF2 frequency > 6.25 Hz Active Low Pulse Width 80 ms CF1 or CF2 frequency < 6.25 Hz Jitter 0.04 % CF1 or CF2 frequency = 1 Hz Output High Voltage, VOH 2.4 V ISOURCE = 500 μA at 25°C Output Low Voltage, VOL 0.4 V ISINK = 8 mA at 25°C REFERENCE Nominal 1.2 V at REF pin REF Input Voltage Range 1.2 V Input Capacitance 10 pF Reference Error ±0.9 mV TA = 25°C Output Impedance 1.45 kΩ Temperature Coefficient 10 ppm/°C CLKIN/CLKOUT PINS All specifications CLKIN = 3.58 MHz Input Clock Frequency 3.58 MHz Crystal Equivalent Series Resistance 30 200 Ω LOGIC INPUTS—RESET, CLKIN, CS, SCLK, MOSI/SCL/Rx, MISO/SDA/Tx Input High Voltage, VINH 2.4 V VDD = 3.3 V ± 10% Input Low Voltage, VINL 0.8 V VDD = 3.3 V ± 10% Input Current, IIN VIN = 0 V −6.5 μA MOSI/SCL/Rx, MISO/SDA/Tx, RESET GCLKIN, CS, SCLK 0 μA MMInput Capacitance, CIN 10 pF VDD = 3.3 V ± 10% LOGIC OUTPUTS—IRQ, REVP, ZX, ZX_I, CLKOUT, MOSI/SCL/Rx, MISO/SDA/Tx Output High Voltage, VOH 3.0 V ISOURCE = 800 μA Output Low Voltage, VOL 0.4 V ISINK = 2 mA POWER SUPPLY For specified performance VDD 3.0 V 3.3 V − 10% 3.6 V 3.3 V + 10% IDD 6.8 mA

Rev. 0 | Page 5 of 68

ADE7953

TIMING CHARACTERISTICS

SPI Interface Timing

VDD = 3.3 V ± 10%, AGND = DGND = 0 V, on-chip reference, CLKIN = 3.58 MHz, TMIN to TMAX = −40°C to +85°C, unless otherwise noted. Table 2.

Parameter Description tCS CS to SCLK edge tSCLK SCLK period tSL SCLK low pulse width tSH SCLK high pulse width tDAV Data output valid after SCLK edge tDSU Data input setup time before SCLK edge tDHD Data input hold time after SCLK edge tDF Data output fall time tDR Data output rise time tSR SCLK rise time tSF SCLK fall time tDIS MISO disabled after CS rising edge tSFS CS high after SCLK edge tSFS_LK CS high after SCLK edge (when writing to

COMM_LOCK bit)

in1Max150 200 80 80 80 70 5 20 20 20 20 5 40 0

1200

Unit ns

ns ns ns ns ns ns ns ns ns ns ns ns

Min and max values are typical minimum and maximum values.

SPI Interface Timing Diagram

MtCStSCLKtSFS_LKtSFSSCLK

tSLtDAVtSHtSFtSRtDISMISO

MSB OUTINTERMEDIATE BITSLSB OUTtDFINTERMEDIATE BITSMOSI

MSB INtDRLSB IN09320-003tDSUtDHD

Figure 2. SPI Interface Timing

Rev. 0 | Page 6 of 68

ADE7953

I2C Interface Timing

VDD = 3.3 V ± 10%, AGND = DGND = 0 V, on-chip reference, CLKIN = 3.58 MHz, TMIN to TMAX = −40°C to +85°C, unless otherwise noted. Table 3.

Parameter Description fSCL SCL clock frequency tHD;STA Hold time for a start or repeated start condition tLOW Low period of SCL clock tHIGH High period of SCL clock tSU;STA Setup time for a repeated start condition tHD;DAT Data hold time tSU;DAT Data setup time tR Rise time of SDA and SCL signals tF Fall time of SDA and SCL signals tSU;STO Setup time for stop condition tBUF Bus-free time between a stop and start condition tSP Pulse width of suppressed spikes

Standard Mode Fast Mode

111

in ax in ax Unit 0 100 0 400 kHz 4.0 0.6 μs 4.7 1.3 μs 4.0 0.6 μs 4.7 0.6 μs 0 3.45 0 0.9 μs 250 100 ns 1000 20 300 ns 300 20 300 ns 4.0 0.6 μs 4.7 1.3 μs N/A 50 ns

Min and max values are typical minimum and maximum values.

I2C Interface Timing Diagram

SDAtFtLOWSCLtSU;DATtRtFMMtHD;STAMtSPtRtBUFMtHD;STASTARTCONDITIONtHD;DATREPEATED STARTCONDITIONSTOPSTARTCONDITIONCONDITION09320-002tHIGHtSU;STAtSU;STO

Figure 3. IC Interface Timing

Rev. 0 | Page 7 of 68

ADE7953

Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational

section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability.

ABSOLUTE MAXIMUM RATINGS

TA = 25°C, unless otherwise noted. Table 4.

Parameter Rating VDD to AGND −0.3 V to +3.7 V VDD to DGND −0.3 V to +3.7 V

−2 V to +2 V Analog Input Voltage to AGND,

IAP, IAN, IBP, IBN, VP, VN

Reference Input Voltage to AGND −0.3 V to VDD + 0.3 V Digital Input Voltage to DGND −0.3 V to VDD + 0.3 V Digital Output Voltage to DGND −0.3 V to VDD + 0.3 V Operating Temperature Industrial Range −40°C to +85°C Storage Temperature Range −65°C to +150°C

ESD CAUTION

Rev. 0 | Page 8 of 68

ADE7953

PIN CONFIGURATION AND FUNCTION DESCRIPTIONS

27MOSI/SCL/Rx26MISO/SDA/Tx25SCLK24CF223CF128CS22IRQZX1RESET2VINTD3DGND4IAP5IAN6PULL_HIGH789IBN10VN11VP12REF13PULL_LOW1421ZX_IADE7953TOP VIEW(Not to Scale)20REVP19CLKOUT18CLKIN17VDD16AGND15VINTAPULL_HIGHIBPNOTES1. CREATE A SIMILARPAD ON THE PCB UNDER THE EXPOSEDPAD. SOLDER THE EXPOSEDPADTO THEPAD ON THE PCBTO CONFER MECHANICAL STRENGTHTO THEPACKAGE. DO NOT CONNECT THEPADSTOAGND.

Figure 4. Pin Configuration

Table 5. Pin Function Descriptions Pin No. Mnemonic Description 1 ZX Voltage Channel Zero-Crossing Output Pin. See the Voltage Channel Zero Crossing section. This pin can be configured to output a range of alternative power quality signals (see the Alternative Output Functions section). 2 Active Low Reset Input. RESET3 VINTD This pin provides access to the 2.5 V digital LDO. This pin should be decoupled with a 4.7 μF capacitor in parallel with a 100 nF ceramic capacitor. 4 DGND Ground Reference for the Digital Circuitry. 5, 6 IAP, IAN Analog Input for Current Channel A (Phase Current Channel). This differential voltage input has a maximum input range of ±500 mV. The maximum pin voltage for single-ended use is ±250 mV. The PGA associated with this input has a maximum gain stage of 22 (see the Analog Inputs section). 7, 8 PULL_HIGH These pins should be connected to VDD for proper operation. 9, 10 IBP, IBN Analog Input for Current Channel B (Neutral Current Channel). This differential voltage input has a maximum input range of ±500 mV. The PGA associated with this input has a maximum gain of 16 (see the Analog Inputs section). 11, 12 VN, VP Analog Input for Voltage Channel. This single-ended voltage input has a maximum input range of ±500 mV. The PGA associated with this input has a maximum gain of 16 (see the Analog Inputs section). 13 REF This pin provides access to the on-chip voltage reference. The internal reference has a nominal voltage of 1.2 V. This pin should be decoupled with a 4.7 μF capacitor in parallel with a 100 nF ceramic capacitor. Alternatively, an external reference voltage of 1.2 V can be applied to this pin (see the Reference Circuit section). 14 PULL_LOW This pin should be connected to AGND for proper operation. 15 VINTA This pin provides access to the 2.5 V analog LDO. This pin should be decoupled with a 4.7 μF capacitor in parallel with a 100 nF ceramic capacitor. 16 AGND Ground Reference for the Analog Circuitry. 17 VDD Power Supply (3.3 V) for the ADE7953. For specified operation, the input to this pin should be within 3.3 V ± 10%. This pin should be decoupled with a 10 μF capacitor in parallel with a 100 nF ceramic capacitor. 18 CLKIN Master Clock Input for the ADE7953. An external clock can be provided at this input. Alternatively, a parallel resonant AT crystal can be connected across the CLKIN and CLKOUT pins to provide a clock source for the ADE7953. The clock frequency for specified operation is 3.58 MHz. Ceramic load capacitors of a few tens of picofarads should be used with the gate oscillator circuit. Refer to the crystal manufacturer’s data sheet for the load capacitance requirements. 19 CLKOUT A crystal can be connected across this pin and CLKIN to provide a clock source for the ADE7953. Rev. 0 | Page 9 of 68

09320-004ADE7953

Mnemonic REVPPin No. 20 Description Reverse Power Output Indicator. See the Reverse Power section. This pin can be configured to output a range of alternative power quality signals (see the Alternative Output Functions section). 21 ZX_I Current Channel Zero-Crossing Output Pin. See the Current Channel Zero Crossing section. This pin can be configured to output a range of alternative power quality signals (see the Alternative Output Functions section). 22 Interrupt Output. See the ADE7953 Interrupts section. IRQ23 CF1 Calibration Frequency Output 1. 24 CF2 Calibration Frequency Output 2. 25 SCLK Serial Clock Input for the Serial Peripheral Interface. All serial communications are synchronized to the clock (see the SPI Interface section). If using the I2C interface, this pin must be pulled high. If using the UART interface, this pin must be pulled to ground. 26 MISO/SDA/Tx Data Output for SPI Interface/Bidirectional Data Line for I2C Interface/Transmit Line for UART Interface. 27 MOSI/SCL/Rx Data Input for SPI Interface/Serial Clock Input for I2C Interface/Receive Line for UART Interface. 28 CS Chip Select for SPI Interface. This pin must be pulled high if using the I2C or UART interface. EPAD Exposed Pad. Create a similar pad on the PCB under the exposed pad. Solder the exposed pad to the pad on the PCB to confer mechanical strength to the package. Do not connect the pads to AGND.

Rev. 0 | Page 10 of 68

ADE7953

TYPICAL PERFORMANCE CHARACTERISTICS

1.00.80.6–40°C+25°C+85°C1.00.80.6ERROR (% OF READING)ERROR (% OF READING)PF = –0.5PF = +0.5PF = +1.00.40.20–0.2–0.4–0.6–0.80.0010.010.1109320-1010.40.20–0.2–0.4–0.6–0.80.0010.010.1109320-10409320-106–1.00.0001–1.00.0001CURRENT CHANNEL (% FULL SCALE)CURRENT CHANNEL (% FULL SCALE)Figure 5. Current Channel A Active Energy Error as a Percentage of Reading (Gain = 1, Power Factor = 1) over Temperature with Internal Reference,

Integrator Off

1.00.80.6ERROR (% OF READING)Figure 8. Current Channel A Active Energy Error as a Percentage of Reading (Gain = 22, Temperature = 25°C) over Power Factor with Internal Reference,

Integrator Off

1.00.80.40.20–0.2–0.4–0.6–0.809320-102ERROR (% OF READING)PF = –0.5PF = +0.5PF = +1.00.60.40.20–0.2–0.4–0.6–0.8VDD = 3.30VVDD = 2.97VVDD = 3.63V0.0010.010.110.0010.010.11CURRENT CHANNEL (% FULL SCALE)CURRENT CHANNEL (% FULL SCALE)Figure 6. Current Channel A Active Energy Error as a Percentage of Reading (Gain = 1, Temperature = 25°C) over Power Factor with Internal Reference,

Integrator Off

1.00.80.6ERROR (% OF READING)Figure 9. Current Channel A Active Energy Error as a Percentage of Reading (Gain = 22, Temperature = 25°C, Power Factor = 1) over Supply Voltage

with Internal Reference, Integrator Off

1.00.8

PF = –0.5PF = +0.5PF = +1.0ERROR (% OF READING)–40°C+25°C+85°C0.60.40.20–0.2–0.4–0.6–0.8

0.40.20–0.2–0.4–0.6–0.80.0010.010.1109320-103–1.00.0001– 1.0

FREQUENCY (Hz)

CURRENT CHANNEL (% FULL SCALE)Figure 7. Current Channel A Active Energy Error as a Percentage of Reading (Gain = 22, Power Factor = 1) over Temperature with Internal Reference,

Integrator Off Figure 10. Current Channel A Active Energy Error as a Percentage of Reading

(Gain = 22, Temperature = 25°C) over Frequency and Power Factor

with Internal Reference, Integrator Off

Rev. 0 | Page 11 of 68

09320-105–1.00.0001–1.00.0001ADE7953

1.00.80.6ERROR (% OF READING)

1.00.8–40°C+25°C+85°C0.6ERROR (% OF READING)PF = –0.866PF = 0PF = +0.8660.40.20–0.2–0.4–0.6–0.809320-1070.40.20–0.2–0.4–0.6–0.80.0010.010.110.0010.010.11CURRENT CHANNEL (% FULL SCALE)CURRENT CHANNEL (% FULL SCALE)Figure 11. Current Channel A Reactive Energy Error as a Percentage of Reading (Gain = 1, Power Factor = 0) over Temperature with Internal Reference,

Integrator Off

1.00.80.6ERROR (% OF READING)Figure 14. Current Channel A Reactive Energy Error as a Percentage of Reading (Gain = 22, Temperature = 25°C) over Power Factor with Internal Reference,

Integrator Off

1.00.8

PF = –0.866PF = 0PF = +0.866ERROR (% OF READING)PF = –0.866PF = 0PF = +0.8660.60.40.20–0.2–0.4–0.6–0.8

0.40.20–0.2–0.4–0.6–0.80.0010.010.1109320-108–1.00.0001– 1.0

FREQUENCY (Hz)

CURRENT CHANNEL (% FULL SCALE)Figure 12. Current Channel A Reactive Energy Error as a Percentage of Reading (Gain = 1, Temperature = 25°C) over Power Factor with Internal Reference,

Integrator Off

1.00.80.6ERROR (% OF READING)Figure 15. Current Channel A Reactive Energy Error as a Percentage of Reading

(Gain = 22, Temperature = 25°C) over Frequency and Power Factor

with Internal Reference, Integrator Off

1.0–40°C+25°C+85°CERROR (% OF READING)0.80.60.40.20–0.2–0.4–0.6–0.809320-109GAIN = 1GAIN = 220.40.20–0.2–0.4–0.6–0.8–1.00.00010.0010.010.110.010.11CURRENT CHANNEL (% FULL SCALE)CURRENT CHANNEL (% FULL SCALE)Figure 13. Current Channel A Reactive Energy Error as a Percentage of Reading (Gain = 22, Power Factor = 0) over Temperature with Internal Reference,

Integrator Off Figure 16. Current Channel A IRMS Error as a Percentage of Reading (Temperature = 25°C, Power Factor = 1) over Gain with Internal Reference,

Integrator Off

Rev. 0 | Page 12 of 68

09320-112–1.00.00109320-11109320-110–1.00.0001–1.00.0001

1.00.80.6ERROR (% OF READING)1.00.8

PF = –0.5PF = +0.5PF = +1.0ADE7953

–40°C+25°C+85°C0.6ERROR (% OF READING)0.40.20–0.2–0.4–0.6–0.8

0.40.20–0.2–0.4–0.6–0.80.010.1109320-113–1.00.001– 1.0

FREQUENCY (Hz)

CURRENT CHANNEL (% FULL SCALE)Figure 17. Current Channel B Active Energy Error as a Percentage of Reading (Gain = 1, Power Factor = 1) over Temperature with Internal Reference,

Integrator Off

1.00.80.6ERROR (% OF READING)Figure 20. Current Channel B Active Energy Error as a Percentage of Reading

(Gain = 1, Temperature = 25°C) over Frequency and Power Factor

with Internal Reference, Integrator Off

1.00.80.40.20–0.2–0.4–0.6–0.809320-114ERROR (% OF READING)PF = –0.5PF = +0.5PF = +1.00.60.40.20–0.2–0.4–0.6–0.80.010.11–40°C+25°C+85°C0.010.11CURRENT CHANNEL (% FULL SCALE)CURRENT CHANNEL (% FULL SCALE)Figure 18. Current Channel B Active Energy Error as a Percentage of Reading (Gain = 1, Temperature = 25°C) over Power Factor with Internal Reference,

Integrator Off

1.00.80.6ERROR (% OF READING)Figure 21. Current Channel B Reactive Energy Error as a Percentage of Reading (Gain = 1, Power Factor = 0) over Temperature with Internal Reference,

Integrator Off

1.00.8ERROR (% OF READING)VDD = 3.30VVDD = 2.97VVDD = 3.63V0.60.40.20–0.2–0.4–0.6–0.809320-115PF = –0.866PF = 0PF = +0.8660.40.20–0.2–0.4–0.6–0.8–1.00.0010.010.110.010.11CURRENT CHANNEL (% FULL SCALE)CURRENT CHANNEL (% FULL SCALE)Figure 19. Current Channel B Active Energy Error as a Percentage of Reading (Gain = 1, Temperature = 25°C, Power Factor = 1) over Supply Voltage

with Internal Reference, Integrator Off Figure 22. Current Channel B Reactive Energy Error as a Percentage of Reading (Gain = 1, Temperature = 25°C) over Power Factor with Internal Reference,

Integrator Off

Rev. 0 | Page 13 of 68

09320-118–1.00.00109320-117–1.00.001–1.00.00109320-116ADE7953

1.00.80.6ERROR (% OF READING)0.40.20–0.2–0.4–0.6–0.8– 1.0

FREQUENCY (Hz)

09320-219

1.0PF = –0.866PF = 0PF = +0.8660.80.6ERROR (% OF READING)–40°C+25°C+85°C0.40.20–0.2–0.4–0.6–0.80.0010.010.1109320-12209320-12409320-12365

–1.00.0001CURRENT CHANNEL (% FULL SCALE)Figure 23. Current Channel B Reactive Energy Error as a Percentage of Reading

(Gain = 1, Temperature = 25°C) over Frequency and Power Factor

with Internal Reference, Integrator Off

1.00.80.6ERROR (% OF READING)Figure 26. Current Channel A Active Energy Error as a Percentage of Reading (Gain = 16, Power Factor = 1) over Temperature with Internal Reference,

Integrator On

1.00.80.6ERROR (% OF READING)PF = –0.5PF = +0.5PF = +1.00.40.20–0.2–0.4–0.6–0.80.010.1109320-2200.40.20–0.2–0.4–0.6–0.8–1.00.00010.0010.010.11–1.00.001CURRENT CHANNEL (% FULL SCALE)CURRENT CHANNEL (% FULL SCALE)Figure 24. Current Channel B IRMS Error as a Percentage of Reading

(Gain = 1, Temperature = 25°C, Power Factor = 1)

with Internal Reference, Integrator Off

1.00.80.6ERROR (% OF READING)Figure 27. Current Channel A Active Energy Error as a Percentage of Reading (Gain = 16, Temperature = 25°C) over Power Factor with Internal Reference,

Integrator On

1.00.80.6ERROR (% OF READING)–40°C+25°C+85°C0.40.20–0.2–0.4–0.6–0.80.010.1109320-1210.40.20–0.2–0.4–0.6–0.8–1.00.0010.010.11–1.00.001VOLTAGE CHANNEL (% FULL SCALE)CURRENT CHANNEL (% FULL SCALE)Figure 25. VRMS Error as a Percentage of Reading (Temperature = 25°C,

Power Factor = 1) with Internal Reference, Integrator Off

Figure 28. Current Channel B Active Energy Error as a Percentage of Reading (Gain = 16, Power Factor = 1) over Temperature with Internal Reference,

Integrator On

Rev. 0 | Page 14 of 68

1.00.80.6ERROR (% OF READING)ADE7953

1.00.8PF = –0.5PF = +0.5PF = +1.00.6ERROR (% OF READING)–40°C+25°C+85°C0.40.20–0.2–0.4–0.6–0.809320-2250.40.20–0.2–0.4–0.6–0.80.010.110.010.11CURRENT CHANNEL (% FULL SCALE)CURRENT CHANNEL (% FULL SCALE)Figure 29. Current Channel B Active Energy Error as a Percentage of Reading (Gain = 16, Temperature = 25°C) over Power Factor with Internal Reference,

Integrator On

1.00.80.6ERROR (% OF READING)Figure 32. Current Channel B Reactive Energy Error as a Percentage of Reading (Gain = 16, Power Factor = 0) over Temperature with Internal Reference,

Integrator On

1.00.80.40.20–0.2–0.4–0.6–0.809320-126ERROR (% OF READING)–40°C+25°C+85°C0.60.40.20–0.2–0.4–0.6–0.8PF = –0.866PF = 0PF = +0.8660.0010.010.110.010.11CURRENT CHANNEL (% FULL SCALE)CURRENT CHANNEL (% FULL SCALE)Figure 30. Current Channel A Reactive Energy Error as a Percentage of Reading (Gain = 16, Power Factor = 0) over Temperature with Internal Reference,

Integrator On

1.00.80.6ERROR (% OF READING)Figure 33. Current Channel B Reactive Energy Error as a Percentage of Reading (Gain = 16, Temperature = 25°C) over Power Factor with Internal Reference,

Integrator On

1.00.8CHANNEL ACHANNEL BERROR (% OF READING)PF = –0.866PF = 0PF = +0.8660.60.40.20–0.2–0.4–0.6–0.809320-2270.40.20–0.2–0.4–0.6–0.8–1.00.00010.0010.010.110.010.11CURRENT CHANNEL (% FULL SCALE)CURRENT CHANNEL (% FULL SCALE)Figure 31. Current Channel A Reactive Energy Error as a Percentage of Reading (Gain = 16, Temperature = 25°C) over Power Factor with Internal Reference,

Integrator On

Figure 34. IRMS Error as a Percentage of Reading (Gain = 16, Temperature = 25°C) with Internal Reference, Integrator On

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09320-130–1.00.00109320-129–1.00.0001–1.00.00109320-228–1.00.001–1.00.001ADE7953

TEST CIRCUIT

3.3V3.3V10kΩ1kΩ33nF33nF1kΩ1kΩ33nF33nF1kΩ9104.7µF1µF+0.1µF15173+4.7µF0.1µFVINTA256RESETIAPIANVINTDVDDZX1REVP20ZX_I21CS28MOSI/SCL/Rx27IBPIBNMISO/SDA/Tx26SCLK2510kΩSAME ASCF23.3V10kΩIRQ22REF1320pFCLKOUT19DGNDAGND3.3VADE795333nF11CF224CF1231.5kΩ1kΩ1MΩ110V1kΩVNVPPULL_HIGHPULL_HIGHPULL_LOW1233nF3.3V78144.7µF+0.1µF3.58MHzCLKIN1820pF09320-099416

Figure 35. Test Circuit

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ADE7953

TERMINOLOGY

Measurement Error

The error associated with the energy measurement made by the ADE7953 is defined by

ADC Offset Error

The ADC offset error refers to the dc offset associated with the analog inputs to the ADCs. It means that, with the analog inputs connected to AGND, the ADCs still see a dc analog input signal. Measurement Error = (1)

The magnitude of the offset depends on the gain and input range

Energy Registered by ADE7953 − True Energy

×100% selection. However, the offset is removed from the current and

TrueEnergy

voltage channels by a high-pass filter (HPF), and the power calculation is not affected by this offset. Phase Error Between Channels

The high-pass filter (HPF) and digital integrator introduce a Gain Error slight phase mismatch between the current channels and the The gain error in the ADCs of the ADE7953 is defined as the voltage channel. The all-digital design ensures that the phase per-channel difference between the measured ADC output code matching between the current channels and the voltage channel (minus the offset) and the ideal output code (see the Current is within ±0.05° over a range of 45 Hz to 65 Hz. This internal Channel ADCs section and the Voltage Channel ADC section). phase mismatch can be combined with the external phase error The difference is expressed as a percentage of the ideal code. (from current sensor or component tolerance) and calibrated with the phase calibration registers.

Power Supply Rejection (PSR)

PSR quantifies the ADE7953 measurement error as a percentage of reading when the power supplies are varied. For the ac PSR measurement, a reading at nominal supplies (3.3 V) is taken. A second reading is obtained with the same input signal levels when an ac signal (120 mV rms/100 Hz) is introduced onto the supplies. Any error introduced by this ac signal is expressed as a percentage of reading (see the Measurement Error definition). For the dc PSR measurement, a reading at nominal supplies (3.3 V) is taken. A second reading is obtained with the same input signal levels when the power supplies are varied by ±10%. Any error introduced is again expressed as a percentage of reading.

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ADE7953

The voltage channel gain is configured by writing to the PGA_V register (Address 0x007). By default, the voltage channel PGA is set to 1.

Table 6. PGA Gain Settings

Full-Scale Differential

Gain Input (mV) 1 ±500 2 ±250 4 ±125 8 ±62.5 16 ±31.25 22 ±22.7 1

THEORY OF OPERATION

ANALOG INPUTS

The ADE7953 includes three analog inputs that form two current channels and one voltage channel. In a standard configuration, Current Channel A is used to measure the phase current, and Current Channel B is used to measure the neutral current. The voltage channel input measures the difference between the phase voltage and the neutral voltage. The ADE7953 can, however, be used with alternative voltage and current combinations as long as the analog input specifications described in this section are met.

Current Channel A

Current Channel A is a fully differential voltage input that is designed to be used with a current sensor. This input is driven by two pins: IAP (Pin 5) and IAN (Pin 6). The maximum differ-ential voltage that can be applied to IAP and IAN is ±500 mV. A common-mode voltage of less than ±25 mV is recommended. Common-mode voltages in excess of this recommended value may limit the available dynamic range. A programmable gain amplifier (PGA) stage is provided on Current Channel A with gain options of 1, 2, 4, 8, 16, and 22 (see Table 6).

The maximum full-scale input of Current Channel A is ±250 mV when using a single-ended configuration and, therefore, when using a gain setting of 1, the dynamic range is limited. The Current Channel A gain is configured by writing to the PGA_IA register (Address 0x008). By default, the Current Channel A PGA is set to 1. A gain option of 22 is offered exclusively on Current

Channel A, allowing high accuracy measurement for signals of very small amplitude. This configuration is particularly useful when using small value shunt resistors or Rogowski coils.

PGA_IA[2:0] PGA_IB[2:0] PGA_V[2:0] (Addr 0x008) (Addr 0x009) (Addr 0x007) 0001 000 000 001 001 001 010 010 010 011 011 011 100 100 100 101 N/A N/A

When a gain of 1 is selected on Current Channel A, the maximum pin input is

limited to ±250 mV. Therefore, when using a single-ended configuration, the maximum input is ±250 mV with respect to AGND.

ANALOG-TO-DIGITAL CONVERSION

The analog-to-digital conversion in the ADE7953 is performed by three second-order Σ-Δ modulators. For the sake of clarity, the block diagram in Figure 36 shows the operation of a first-order Σ-Δ modulator. The analog-to-digital conversion consists of a Σ-Δ modulator followed by a low-pass filter stage.

CLKIN/4ANALOGLOW-PASS FILTERRC+–+VREFDIGITALLOW-PASSFILTER24INTEGRATOR+–LATCHEDCOMPARATORCurrent Channel B

Current Channel B is a fully differential voltage input that is designed to be used with a current sensor. This input is driven by two pins: IBP (Pin 9) and IBN (Pin 10). The maximum differ-ential voltage that can be applied to IBP and IBN is ±500 mV. A common-mode voltage of less than ±25 mV is recommended. Common-mode voltages in excess of this recommended value may limit the available dynamic range. A PGA gain stage is provided on Current Channel B with gain options of 1, 2, 4, 8, and 16 (see Table 6). The Current Channel B gain is configured by writing to the PGA_IB register (Address 0x009). By default, the Current Channel B PGA is set to 1.

–VREF09320-013.....10100101.....1-BIT DAC

Figure 36. Σ-Δ Conversion

Voltage Channel

The voltage channel input is a single-ended input driven by two pins: VP (Pin 12) and VN (Pin 11). The maximum single-ended voltage that can be applied to VP is ±500 mV with respect to VN. A common-mode voltage of less than ±25 mV is recommended. Common-mode voltages in excess of this recommended value may limit the dynamic range capabilities of the ADE7953. A PGA gain stage is provided on the voltage channel with gain options of 1, 2, 4, 8, and 16 (see Table 6).

The Σ-Δ modulator converts the input signal into a continuous serial stream of 1s and 0s at a rate determined by the sampling clock. The ADE7953 sampling clock is equal to 895 kHz

(CLKIN/4). The 1-bit DAC in the feedback loop is driven by the serial data stream. The DAC output is subtracted from the input signal. If the loop gain is high enough, the average value of the DAC output (and, therefore, the bit stream) can approach that of the input signal level. For any given input value in a single sampling interval, the data from the 1-bit ADC is virtually meaningless. A meaningful result is obtained only when a large number of samples is averaged. This averaging is carried out in the second part of the ADC, the digital low-pass filter. By averaging a large number of bits from the modulator, the low-pass filter can produce 24-bit data-words that are proportional to the input signal level.

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ADE7953

Noise Shaping

Noise shaping is the second technique used to achieve high resolution. In the Σ-Δ modulator, the noise is shaped by the integrator, which has a high-pass-type response for the quanti-zation noise due to feedback. The result is that most of the noise is at the higher frequencies, where it can be removed by the digital low-pass filter. This noise shaping is shown in Figure 37.

The Σ-Δ converter uses two techniques—oversampling and noise shaping—to achieve high resolution from what is essentially a 1-bit conversion technique.

Oversampling

Oversampling is the first technique used to achieve high

resolution. Oversampling means that the signal is sampled at a rate (frequency) that is many times higher than the bandwidth of interest. For example, the sampling rate in the ADE7953 is 895 kHz, and the bandwidth of interest is 40 Hz to 1.23 kHz. Oversampling has the effect of spreading the quantization noise (noise due to sampling) over a wider bandwidth. With the noise spread more thinly over a wider bandwidth, the quantization noise in the band of interest is lowered (see Figure 37).

SIGNALANTIALIASING FILTER(RC)DIGITAL FILTERSHAPED NOISESAMPLINGFREQUENCYAntialiasing Filter

As shown in Figure 36, an external low-pass RC filter is required on the input to each modulator. The role of this filter is to prevent aliasing. Aliasing refers to the frequency components in the input signal that are folded back and appear in the sampled signal. This effect occurs with signals that are higher than half the sampling rate of the ADC (also known as the Nyquist frequency) appear-ing in the sampled signal at a frequency below half the sampling rate. This concept is depicted in Figure 38.

ALIASING EFFECTSSAMPLINGFREQUENCYNOISE03447.5FREQUENCY (kHz)89509320-015SIGNALHIGH RESOLUTIONOUTPUT FROMDIGITAL LPF01.233447.5895FREQUENCY (kHz)IMAGEFREQUENCIES

NOISE09320-014Figure 38. Aliasing Effect

03447.5FREQUENCY (kHz)895

Figure 37. Noise Reduction due to Oversampling and

Noise Shaping in the Analog Modulator

The arrows shown in Figure 38 depict the frequency compo-nents above the Nyquist frequency (447.5 kHz in the case of the ADE7953) being folded back down. Aliasing occurs with all ADCs, regardless of the architecture.

However, oversampling alone is not sufficient to improve the signal-to-noise ratio (SNR) in the bandwidth of interest. For example, an oversampling ratio of 4 is required to increase the SNR by only 6 dB (1 bit). To keep the oversampling ratio at a reasonable level, it is possible to shape the quantization noise so that the majority of the noise lies at the higher frequencies (see the Noise Shaping section).

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ADE7953

LPF1ZX_I DETECTIONCURRENT PEAK,OVERCURRENTDETECTIONDSPPGA_x BITS×1, ×2, ×4, ×8, ×16,×22 (FOR IA ONLY)PGAREFERENCExIGAINHPFEN BITCONFIG[2]INTENx BITCONFIG[1:0]DIGITALINTEGRATORHPFCURRENT RMS (IRMS)CALCULATIONIxWAVEFORMSAMPLING REGISTERACTIVEAND REACTIVEPOWER CALCULATION

IxPVINIxN09320-019ADC

Figure 39. Current Channel ADC and Signal Path

CURRENT CHANNEL ADCs

Figure 39 shows the ADC signal path and signal processing for Current Channel A, which is accessed through the IAP and IAN pins. The signal path for Current Channel B is identical and is accessed through the IBP and IBN pins. The ADC output is a twos complement, 24-bit data-word that is available at a rate of 6.99 kSPS (thousand samples per second). With the specified full-scale analog input of ±250 mV and a PGA_Ix gain setting of 2, the ADC produces its maximum output code. The ADC output swings between −6,500,000 LSBs (decimal) and +6,500,000 LSBs. This output varies from part to part.

As shown in Figure 39, there is a high-pass filter (HPF) in each current channel signal path. The HPF is enabled by default and removes any dc offset in the ADC output. It is highly recom-mended that this filter be enabled at all times, but it can be disabled by clearing the HPFEN bit (Bit 2) in the CONFIG register (Address 0x102). Clearing the HPFEN bit disables the filters in both current channels and in the voltage channel.

MAGNETIC FIELD CREATED BY CURRENT(DIRECTLY PROPORTIONALTO CURRENT)09320-020+ EMF (ELECTROMOTIVE FORCE)– INDUCED BY CHANGES INMAGNETIC FLUX DENSITY (di/dt)

Figure 40. Principle of a di/dt Current Sensor

di/dt Current Sensor and Digital Integrator

As shown in Figure 39, the current channel signal path for both Channel A and Channel B includes an internal digital integrator. This integrator is disabled by default and is required only when interfacing with a di/dt sensor, such as a Rogowski coil. When using either a shunt resistor or a current transformer (CT), this integrator is not required and should remain disabled.

A di/dt sensor detects changes in the magnetic field caused by ac current. Figure 40 shows the principle of a di/dt current sensor.

The flux density of a magnetic field induced by a current is directly proportional to the magnitude of the current. Changes in the magnetic flux density passing through a conductor loop generate an electromotive force (EMF) between the two ends of the loop. The EMF is a voltage signal that is proportional to the differential of the current over time (di/dt). The voltage output from the di/dt sensor is determined by the mutual inductance between the current-carrying conductor and the di/dt sensor. The current signal must be recovered from the di/dt signal before it can be used. An integrator is therefore necessary to restore the signal to its original form.

The ADE7953 has a built-in digital integrator on each current channel that recovers the current signal from the di/dt sensor. Both digital integrators are disabled by default. The digital integrator on Current Channel A is enabled by setting the INTENA bit (Bit 0) in the CONFIG register (Address 0x102). The digital integrator on Current Channel B is enabled by setting the INTENB bit (Bit 1) in the CONFIG register (Address 0x102).

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ADE7953

REFERENCE CIRCUIT

The ADE7953 has an internal voltage reference of 1.2 V nominal, which appears on the REF pin. This reference voltage is used by the ADCs in the ADE7953. The REF pin can be overdriven by an external source, for example an external 1.2 V reference. The voltage of the ADE7953 internal reference drifts slightly over temperature (see the Specifications section). The value of the tem-perature drift may vary slightly from part to part. A drift of x% in the reference results in a 2x% deviation in meter accuracy. The reference drift is typically minimal and is usually much smaller than the drift of other components in the meter. By default, the ADE7953 is configured to use the internal reference. If Bit 0 of the EX_REF register (Address 0x800) is set to 1, an external voltage reference can be applied to the REF pin.

VOLTAGE CHANNEL ADC

Figure 41 shows the ADC signal path and signal processing for the voltage channel input, which is accessed through the VP and VN pins. The ADC output is a twos complement, 24-bit data-word that is available at a rate of 6.99 kSPS (thousand samples per second). With the specified full-scale analog input of ±500 mV and a PGA_V gain setting of 1, the ADC produces its maximum output code. The ADC output swings between −6,500,000 LSBs (decimal) and +6,500,000 LSBs. Note that this output varies from part to part.

As shown in Figure 41, there is a high-pass filter (HPF) in the voltage channel signal path. The HPF is enabled by default and removes any dc offset in the ADC output. It is highly recom-mended that this filter be enabled at all times, but it can be disabled by clearing the HPFEN bit (Bit 2) in the CONFIG register (Address 0x102). Clearing the HPFEN bit disables the filters in both current channels and in the voltage channel.

VOLTAGE PEAK,OVERVOLTAGE,SAG DETECTIONDSPPGA_V BITS×1, ×2, ×4, ×8, ×16PGAREFERENCEVGAINHPFEN BITCONFIG[2]VOLTAGE RMS (VRMS)CALCULATIONVWAVEFORMSAMPLING REGISTERACTIVEAND REACTIVEPOWER CALCULATIONVPVINVNADCHPFLPF1ZX DETECTION09320-025

Figure 41. Voltage Channel ADC and Signal Path

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ADE7953

As shown in Figure 42, the current channel ADC output samples are used to continually compute the rms. The rms is achieved by low-pass filtering the square of the output signal and then taking a square root of the result. The 24-bit unsigned rms measurements for Current Channel A and Current Channel B are available in the IRMSA (Address 0x21A and Address 0x31A) and IRMSB (Address 0x21B and Address 0x31B) registers, respectively. Both f2(t)dt (1)

of these registers are updated at a rate of 6.99 kHz.

ROOT MEAN SQUARE MEASUREMENT

Root mean square (rms) is a measurement of the magnitude of an ac signal. Specifically, the rms of an ac signal is equal to the amount of dc required to produce an equivalent amount of power in the load. The rms is expressed mathematically in Equation 1.

RMS =

∫

For time-sampled signals, rms calculation involves squaring the signal, taking the average, and obtaining the square root.

Because the LPF used in the rms signal path is not ideal, it is recommended that the IRMSx registers be read synchronously to the zero-crossing signal (see the Zero-Crossing Detection

1N2

section). This helps to stabilize reading-to-reading variation RMS = ∑f[n] (2)

Nn = 1

by removing the effect of any 2ω ripple present on the rms measurement. As implied by Equation 2, the rms measurement contains

information from the fundamental and all harmonics over VOLTAGE CHANNEL RMS CALCULATION a 1.23 kHz measurement bandwidth.

The ADE7953 provides an rms measurement on the voltage

The ADE7953 provide rms measurements for Current channel. Figure 43 shows the signal path for this calculation. Channel A, Current Channel B, and the voltage channel

VRMSOS[23:0]simultaneously. These measurements have a settling time of approximately 200 ms and are updated at a rate of 6.99 kHz.

212CURRENT CHANNEL RMS CALCULATION

The ADE7953 provides rms measurements for both Current Channel A and Current Channel B. Figure 42 shows the signal path for this calculation. The signal processing is identical for Current Channel A and Current Channel B.

×IRMSOS[23:0]VOLTAGESIGNALFROM HPFX2LPF√VRMS[23:0]09320-041

Figure 43. Voltage Channel RMS Signal Processing

212CURRENTSIGNALFROM HPF ORINTEGRATOR(IF ENABLED)LPF09320-040X2√IRMSx[23:0]

As shown in Figure 43, the voltage channel ADC output samples are used to continually compute the rms. The rms is achieved by low-pass filtering the square of the output signal and then taking a square root of the result. The 24-bit unsigned voltage channel rms measurement is available in the VRMS register (Address 0x21C and Address 0x31C). This register is updated at a rate of 6.99 kHz.

Because the LPF used in the rms signal path is not ideal, it is recommended that the VRMS register be read synchronously to the zero-crossing signal (see the Zero-Crossing Detection section). This helps to stabilize reading-to-reading variation by removing the effect of any 2ω ripple present on the rms measurement.

Figure 42. Current Channel RMS Signal Processing

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ADE7953

ACTIVE POWER CALCULATION

The signal chain for the active power and energy calculations in the ADE7953 is shown in Figure 45. The instantaneous power signal P(t) is generated by multiplying the current and voltage signals. The dc component of the instantaneous power signal is then extracted by LPF2 (low-pass filter) to obtain the active power information. Because LFP2 does not have an ideal “brick

V(t) = 2×V× sin(ωt) (3)

wall” frequency response, the active power signal has some ripple associated with it. This ripple is sinusoidal and has a I(t) = 2×I ×sin(ωt) (4)

frequency equal to twice the line frequency. Because the ripple

where: is sinusoidal in nature, it is removed when the active power V is the rms voltage. signal is integrated to compute the active energy (see the Active I is the rms current. Energy Calculation section).

P(t) = V(t) × I(t) (5) The ADE7953 computes the active power simultaneously on Power is defined as the rate of energy flow from the source to the load. It is defined as the product of the voltage and current waveforms. The resulting waveform is called the instantaneous power signal and is equal to the rate of energy flow at every instant of time. The unit of power is the watt or joules/sec.

Current Channel A and Current Channel B and stores the resulting measurements in the AWATT (Address 0x212 and

The average power over an integral number of line cycles (n)

Address 0x312) and BWATT (Address 0x213 and Address 0x313)

is given by the expression in Equation 7.

registers, respectively. With full-scale inputs, the expected

nT1reading in the AWATT and BWATT registers is approximately P = P(t)dt=VI (7) ∫5,000,000 LSBs (decimal). nT0

P(t) = VI − VI × cos(2ωt)

(6)

where:

P is the active or real power. T is the line cycle period.

The active power is equal to the dc component of the instanta-neous power signal (P(t) in Equation 5). The active power is therefore equal to VI. This relationship is used to calculate active power in the ADE7953. Figure 44 illustrates this concept.

INSTANTANEOUSPOWER SIGNALP(t) = VRMS× IRMS – VRMS × IRMS × cos(2ωt)INSTANTANEOUSACTIVE POWER SIGNAL:VRMS×IRMSVRMS×IRMSThe active power measurements are taken over a bandwidth of 1.23 kHz and include the effects of any harmonics within that range. The active power registers are updated at a rate of 6.99 kHz and can be read using the waveform sampling mode (see the Instantaneous Powers and Waveform Sampling section).

SIGN OF ACTIVE POWER CALCULATION

The active power measurement in the ADE7953 is a signed calcu-lation. If the phase differential between the current and voltage waveforms is more than 90°, the power is negative. Negative power indicates that energy is being injected back into the grid. The ACCMODE register (Address 0x201 and Address 0x301) includes two sign indication bits that show the sign of the active power of Current Channel A (APSIGN_A) and Current Channel B (APSIGN_B). See the Sign Indication section for more information.

0x0 000009320-043I(t) =√2×IRMS×sin(ωt)V(t) =√2×VRMS×sin(ωt)

Figure 44. Active Power Calculation

CURRENTCHANNELA OR BxIGAINDIGITALINTEGRATORHPFPHCALxVGAINLPF2HPFxWGAINxWATTOS+48023AENERGYx0+INTERNALACCUMULATIONFIXED INTERNALTHRESHOLDVOLTAGECHANNELACTIVE POWERSIGNAL09320-044

Figure 45. Active Energy Signal Chain

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ADE7953

AENERGYx[23:0]0x7FFFFFxWGAIN = 0x200000xWGAIN = 0x400000xWGAIN = 0x6000000x3FFFFFACTIVE ENERGY CALCULATION

As described in the Active Power Calculation section, power is defined as the rate of energy flow. This relationship can be expressed mathematically as shown in Equation 8.

P = dE

(8) dt

0x00000019.9539.959.85TIME (Seconds)where: P is power. E is energy.

Conversely, energy is given as the integral of power.

0x40000009320-042E = ∫Pdt (9) 0x800000The ADE7953 achieves the integration of the active power signal in two stages. In the first stage, the active power signals are accumulated in an internal 48-bit register every 143 μs (6.99 kHz) until an internal fixed threshold is reached. When this threshold is reached, a pulse is generated and is accumu-lated in 24-bit, user-accessible accumulation registers. The internal threshold results in a maximum accumulation rate of approximately 210 kHz with full-scale inputs. This process occurs simultaneously on Current Channel A and Current Channel B, and the resulting readings can be read in the 24-bit AENERGYA (Address 0x21E and Address 0x31E) and AENERGYB (Address 0x21F and Address 0x31F) registers. Both stages of the accumulation are signed and, therefore, negative energy is subtracted from positive energy.

Figure 46. Energy Register Roll-Over Time for Active Energy

Note that the energy register contents roll over to full-scale negative (0x800000) and continue to increase in value when the power or energy flow is positive. Conversely, if the power is negative, the energy register underflows to full-scale positive (0x7FFFFF) and continues to decrease in value.

AENERGYA and AENERGYB are read-with-reset registers by default. This means that the contents of these registers are reset to 0 after a read operation. This feature can be disabled by clearing Bit 6 (RSTREAD) of the LCYCMODE register (Address 0x004).

The ADE7953 includes two sets of interrupts that are triggered when the active energy register is half full (positive or negative) or when an overflow or underflow condition occurs. The first This discrete time accumulation, or summation, is equivalent

set of interrupts is associated with the Current Channel A active to integration in continuous time. Equation 10 expresses this

energy, and the second set of interrupts is associated with the relationship.

Current Channel B active energy. These interrupts are disabled

⎧∞⎫by default and can be enabled by setting the AEHFA and E=∫P(t)dt=Lim⎨∑P(nT) × T⎬ (10) T→0⎩n = 1⎭AEOFA bits in the IRQENA register (Address 0x22C and

Address 0x32C) for Current Channel A, and the AEHFB and where:

AEOFB bits in the IRQENB register (Address 0x22F and n is the discrete time-sampled number.

Address 0x32F) for Current Channel B. T is the sample period.

The discrete time sample period (T) for the accumulation

registers in the ADE7953 is 4.76 μs (1/210 kHz). This is illustrated in Figure 46, which shows the energy register roll-over rates with full-scale inputs.

Active Energy Integration Time Under Steady Load

The discrete time sample period (T) for the accumulation registers is 4.76 μs (1/210 kHz). With full-scale sinusoidal signals on the analog inputs and the AWGAIN and BWGAIN registers set to 0x400000, a pulse is generated and added to the AENERGYA and AENERGYB registers every 4.76 μs. The maximum positive value that can be stored in the 24-bit AENERGYA and AENERGYB registers is 0x7FFFFF before the register overflows. The integration time under these conditions can be calculated as follows:

Time = 0x7FFFFF × 4.76 μs = 39.9 sec

(11)

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ADE7953

The number of half line cycles written to the LINECYC register is used for both the Current Channel A and Current Channel B accumulation periods. At the end of a line cycle accumulation cycle, the AENERGYA and AENERGYB registers are updated, and the CYCEND flag is set in the IRQSTATA register (Address 0x22D and Address 0x32D). If the CYCEND bit in the IRQENA register is set, an external interrupt is issued on the IRQ pin. In this way, the IRQ pin can also be used to signal the completion of the line cycle accumulation. Another accumulation cycle begins immediately as long as the ALWATT and BLWATT bits in the LCYCMODE register remain set.

Active Energy Line Cycle Accumulation Mode

In active energy line cycle accumulation mode, the energy accumulation of the ADE7953 is synchronized to the voltage channel zero crossing so that the active energy can be accumu-lated over an integral number of half line cycles. This feature is available for both Current Channel A and Current Channel B active energy. The advantage of summing the active energy over an integral number of half line cycles is that the sinusoidal

component of the active energy is reduced to 0 (see Equation 12 to Equation 15). This eliminates any ripple in the energy calcula-tion. Energy is calculated more accurately and in a shorter time because the integration period can be shortened. The line cycle accumulation mode can be used for fast calibration and also to obtain the average power over a specified time period. Using Equation 6, the following description of the energy accumulation can be derived:

The contents of the AENERGYA and AENERGYB registers are updated synchronous to the CYCEND flag. The AENERGYA and AENERGYB registers hold their current values until the end of the next line cycle period, when the contents are replaced with the new reading. If the read-with-reset bit (RSTREAD) in the LCYCMODE register (Address 0x004) is set, the contents of the P(t) = VI – [LPF] × cos(2ωt) (12)

AENERGYA and AENERGYB registers are cleared after a read nTnT

and remain at 0 until the end of the next line cycle period. E(t) = ∫VIdt − [LPF]×∫cos(2ωt)dt (13)

programmed, ready for the next cycle. This prevents any invalid number of line cycles, its value is always 0. Therefore,

readings due to changes to the LINECYC register (see Figure 47). nT

E(t) = ∫VIdt + 0 (14) where:

n is an integer.

T is the line cycle period.

E = VInt (15) AENERGYx REGISTERLine cycle accumulation mode is disabled by default and can be enabled on Current Channel A and Current Channel B by setting the ALWATT and BLWATT bits to 1 in the LCYCMODE register (Address 0x004). The accumulation time should be written to the LINECYC register (Address 0x101) in the unit of number of half line cycles. The ADE7953 can accumulate energy for up to 65,535 half line cycles. This equates to an accumulation period of approximately 655 sec with 50 Hz inputs and 546 sec with 60 Hz inputs.

xWGAINxWATTOS+480CYCEND IRQLINECYC REGISTERNEW LINE CYCLEVALUE PROGRAMMEDINTERNAL LINE CYCLEUPDATED09320-017

Figure 47. Changing the LINECYC Register

OUTPUT FROMLPF2+INTERNALACCUMULATIONFIXED INTERNALTHRESHOLDOUTPUT FROMVOLTAGE CHANNELADCLPF1ZERO-CROSSINGDETECTIONCALIBRATIONCONTROL23AENERGYx009320-01615LINECYC0

Figure 48. Active Energy Line Cycle Accumulation

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ADE7953

If enabled, the positive-only accumulation mode affects both energy accumulation registers, AENERGYA and AENERGYB, as well as the CF output pins (see the Energy-to-Frequency Conversion section). Note that when the positive-only accumu-lation mode is enabled on a current channel, the reverse power feature is not available on that current channel (see the Reverse Power section).

Note that when line cycle accumulation mode is first enabled, the reading after the first CYCEND flag should be ignored because it may be inaccurate. This is because the line cycle accumulation mode is not synchronized to the zero crossing and, therefore, the first reading may not be over a complete number of half line cycles. After the first line cycle accumulation is complete, all successive readings will be correct.

ACTIVE ENERGY ACCUMULATION MODES

Signed Accumulation Mode

The default active energy accumulation mode for the ADE7953 is a signed accumulation based on the active power information.

Absolute Accumulation Mode

The ADE7953 includes an absolute energy accumulation mode for Current Channel A and Current Channel B active energy. In absolute accumulation mode, the energy accumulation is done using the absolute active power, ignoring any occurrences of energy below the no-load threshold (see Figure 50).

Positive-Only Accumulation Mode

The ADE7953 includes a positive-only accumulation mode option for Current Channel A and Current Channel B active energy. In positive-only accumulation mode, the energy accumulation is done only for positive power, ignoring any occurrence of negative power above or below the no-load threshold (see Figure 49).

AENERGYxNO-LOADTHRESHOLDACTIVE POWER09320-119AENERGYxNO-LOADTHRESHOLD

NO-LOADTHRESHOLDACTIVE POWER09320-018Figure 50. Active Energy Absolute Accumulation Mode

NO-LOADTHRESHOLD

The absolute accumulation mode is disabled by default and can be enabled on Current Channel A and Current Channel B by setting the AWATTACC and BWATTACC bits to 10 in the ACCMODE register (Address 0x201 and Address 0x301). If enabled, the absolute accumulation mode affects both energy accumulation registers, AENERGYA and AENERGYB, as well as the CF output pins (see the Energy-to-Frequency Conversion section). Note that when the absolute accumulation mode is enabled on a current channel, the reverse power feature is not available on that current channel (see the Reverse Power section).

Figure 49. Positive-Only Accumulation Mode

The positive-only accumulation mode is disabled by default and can be enabled on Current Channel A and Current Channel B by setting the AWATTACC and BWATTACC bits to 01 in the ACCMODE register (Address 0x201 and Address 0x301).

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ADE7953

The ADE7953 reactive power measurement is stable over the full frequency range. The dc component of the instantaneous reactive power signal is then extracted by a low-pass filter to obtain the reactive power information.

REACTIVE POWER CALCULATION

Reactive power is defined as the product of the voltage and current waveforms when one of these signals is phase shifted by 90°. The resulting waveform is called the instantaneous reactive power signal.

Equation 16 provides an expression for the instantaneous reactive power signal in an ac system when the phase of the current channel is shifted by +90°.

The frequency response of the LPFs in the reactive power signal paths is identical to the frequency response of the LPFs used in the active power calculation. Because the LPF does not have an ideal “brick wall” frequency response, the reactive power signal (16) RP(t) = V(t) × I’(t)

has some ripple associated with it. This ripple is sinusoidal and

RP(t) = VI × sin(θ) + VI × sin(2ωt + θ) (17) has a frequency equal to twice the line frequency. Because the

ripple is sinusoidal in nature, it is removed when the reactive V(t) = 2×V ×sin(ωt+θ) (18)

power signal is integrated to compute the reactive energy (see

I(t) = 2×I ×sin(ωt) (19) the Reactive Energy Calculation section).

The ADE7953 computes the reactive power simultaneously π⎞

ωt+ (20) I’(t) = 2×I ×sin⎛⎜⎟on Current Channel A and Current Channel B and stores the 2⎠⎝

resulting measurements in the AVAR (Address 0x214 and

where: Address 0x314) and BVAR (Address 0x215 and Address 0x315) V is the rms voltage. registers, respectively. With full-scale inputs, the expected I is the rms current. reading in the AVAR and BVAR registers is approximately θ is the phase difference between the voltage and current channel. 5,000,000 LSBs (decimal). The average reactive power over an integral number of line The reactive power registers are updated at a rate of 6.99 kHz cycles (n) is given by the expression in Equation 21. and can be read using the waveform sampling mode (see the

RP =

nT0

∫RP(t)dt=VI ×sin(θ) (21)

Instantaneous Powers and Waveform Sampling section).

SIGN OF REACTIVE POWER CALCULATION

The reactive power measurement in the ADE7953 is a signed calculation. If the current waveform is leading the voltage wave-form, the reactive power is negative. Negative reactive power indicates a capacitive load. If the current waveform is lagging the voltage waveform, the reactive power is positive. Positive reactive power indicates an inductive load. The ACCMODE register (Address 0x201 and Address 0x301) includes two sign indication bits that show the sign of the reactive power of Current Channel A (VARSIGN_A) and Current Channel B (VARSIGN_B). See the Sign Indication section for more information.

where:

RP is the reactive power. T is the line cycle period.

The reactive power is equal to the dc component of the instantaneous reactive power signal (RP(t) in Equation 16). This relationship is used to calculate reactive power in the ADE7953. The signal chain for the reactive power and energy calculations in the ADE7953 is shown in Figure 51.

The instantaneous reactive power signal RP(t) is generated by multiplying the current signal and the voltage signal. Simulta-neous calculations are performed using Current Channel A and Current Channel B. The multiplication is performed over the full 1.23 kHz bandwidth and results in a reactive power measurement that includes all harmonics included in this range.

CURRENTCHANNELA OR BVOLTAGECHANNELxVARGAIN48REACTIVEPOWERALGORITHMREACTIVEPOWERSIGNAL++023RENERGYx0INTERNALACCUMULATIONFIXED INTERNALTHRESHOLDxVAROS09320-120

Figure 51. Reactive Energy Signal Chain

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ADE7953

Reactive Energy Integration Time Under Steady Load

The discrete time sample period (T) for the accumulation registers is 4.76 μs (1/210 kHz). With full-scale sinusoidal signals on the analog inputs and a phase shift of 90°, a pulse is generated and added to the RENERGYA and RENERGYB registers every 4.76 μs, assuming that the AVARGAIN and BVARGAIN registers are set to 0x00. The maximum positive value that can be stored in the 24-bit RENERGYA and RENERGYB registers is 0x7FFFFF before the register overflows. The integration time under these condi-tions can be calculated as follows:

Time = 0x7FFFFF × 4.76 μs = 39.9 sec

(22)

REACTIVE ENERGY CALCULATION

The ADE7953 achieves the integration of the reactive power signal in two stages. In the first stage, the reactive power signals are accumulated in an internal 48-bit register every 143 μs (6.99 kHz) until an internal fixed threshold is reached. When this threshold is reached, a pulse is generated and is accumu-lated in 24-bit, user-accessible accumulation registers. The internal threshold results in a maximum accumulation rate of approximately 210 kHz with full-scale inputs. This process occurs simultaneously on Current Channel A and Current Channel B, and the resulting readings can be read in the 24-bit RENERGYA (Address 0x220 and Address 0x320) and

RENERGYB (Address 0x221 and Address 0x321) registers. Both stages of the accumulation are signed and, therefore, negative energy is subtracted from positive energy.

Note that the reactive energy register contents roll over to full-scale negative (0x800000) and continue to increase in value when the power or energy flow is positive. Conversely, if the power is negative, the energy register underflows to full-scale positive (0x7FFFFF) and continues to decrease in value. RENERGYA and RENERGYB are read-with-reset registers by default. This means that the contents of these registers are reset to 0 after a read operation. This feature can be disabled by clearing Bit 6 (RSTREAD) of the LCYCMODE register (Address 0x004).

The ADE7953 includes two sets of interrupts that are triggered when the reactive energy register is half full (positive or negative) or when an overflow or underflow condition occurs. The first set of interrupts is associated with the Current Channel A reactive energy, and the second set of interrupts is associated with the Current Channel B reactive energy. These interrupts are disabled by default and can be enabled by setting the VAREHFA and VAREOFA bits in the IRQENA register (Address 0x22C and Address 0x32C) for Current Channel A, and the VAREHFB and VAREOFB bits in the IRQENB register (Address 0x22F and Address 0x32F) for Current Channel B.

xVARGAINxVAROS+Reactive Energy Line Cycle Accumulation Mode

In reactive energy line cycle accumulation mode, the energy accumulation of the ADE7953 is synchronized to the voltage channel zero crossing so that the reactive energy on Current Channel A and Current Channel B can be accumulated over an integral number of half line cycles. Line cycle accumulation mode is disabled by default and can be enabled on Current Channel A and Current Channel B by setting the ALVAR and BLVAR bits to 1 in the LCYCMODE register (Address 0x004). The accumulation time should be written to the LINECYC register (Address 0x101) in the unit of number of half line cycles. The number of half line cycles written to the LINECYC register is used for both the Current Channel A and Current Channel B accumulation periods. The ADE7953 can accumulate reactive energy for up to 65,535 half line cycles. This equates to an accu-mulation period of approximately 655 sec with 50 Hz inputs and 546 sec with 60 Hz inputs.

At the end of a line cycle accumulation cycle, the RENERGYA and RENERGYB registers are updated, and the CYCEND flag in the IRQSTATA register (Address 0x22D and Address 0x32D) is set. If the CYCEND bit in the IRQENA register is set, an external interrupt is issued on the IRQ pin. In this way, the IRQ pin can also be used to signal the completion of the line cycle accumula-tion. Another accumulation cycle begins immediately as long as the ALVAR and BLVAR bits in the LCYCMODE register remain set.

480OUTPUT FROMLPF2+INTERNALACCUMULATIONFIXED INTERNALTHRESHOLDOUTPUT FROMVOLTAGE CHANNELADCLPF1ZERO-CROSSINGDETECTIONCALIBRATIONCONTROL23RENERGYx009320-02115LINECYC0

Figure 52. Reactive Energy Line Cycle Accumulation

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ADE7953

The contents of the RENERGYA and RENERGYB registers are updated synchronous to the CYCEND flag. The RENERGYA and RENERGYB registers hold their current values until the end of the next line cycle period, when the contents are replaced with the new reading. If the read-with-reset bit (RSTREAD) in the LCYCMODE register (Address 0x004) is set, the contents of the RENERGYA and RENERGYB registers are cleared after a read and remain at 0 until the end of the next line cycle period. If a new value is written to the LINECYC register (Address 0x101) midway through a line cycle accumulation, the new value is not internally loaded until the end of a line cycle period. When the LINECYC register is updated mid-reading, the current energy accumulation cycle is completed, and the new value is then programmed, ready for the next cycle. This prevents any invalid readings due to changes to the LINECYC register (see Figure 47). Note that when line cycle accumulation mode is first enabled, the reading after the first CYCEND flag should be ignored because it may be inaccurate. This is because the line cycle accumulation mode is not synchronized to the zero crossing and, therefore, the first reading may not be over a complete number of half line cycles. After the first line cycle accumulation is complete, all successive readings will be correct.

RENERGYxNO-LOADTHRESHOLDREACTIVE POWERNO-LOADTHRESHOLDNO-LOADTHRESHOLDACTIVE POWER09320-02209320-023NO-LOADTHRESHOLD

Figure 53. Reactive Energy Accumulation in Antitamper Accumulation Mode

Absolute Accumulation Mode

The ADE7953 includes an absolute energy accumulation mode for Current Channel A and Current Channel B reactive energy. In absolute accumulation mode, the energy accumulation is done using the absolute reactive power, ignoring any occurrences of energy below the no-load threshold (see Figure 54).

REACTIVE ENERGY ACCUMULATION MODES

Signed Accumulation Mode

The default reactive energy accumulation mode for the ADE7953 is a signed accumulation based on the reactive power information.

Antitamper Accumulation Mode

The ADE7953 includes an antitamper accumulation mode that accumulates reactive energy depending on the sign of the active power. When the active power is positive, the reactive power is added to the reactive energy accumulation register. When the active power is negative, the reactive power is subtracted from the reactive energy accumulation register (see Figure 53). Antitamper accumulation mode is disabled by default and can be enabled on Current Channel A and Current Channel B by setting the AVARACC and BVARACC bits to 01 in the ACCMODE register (Address 0x201 and Address 0x301). If enabled, the antitamper accumulation mode affects both reactive energy accumulation registers, RENERGYA and RENERGYB, as well as the CF output pins (see the Energy-to-Frequency Conversion section).

RENERGYxNO-LOADTHRESHOLDREACTIVE POWERNO-LOADTHRESHOLD

Figure 54. Reactive Energy Absolute Accumulation Mode

The absolute accumulation mode is disabled by default and can be enabled on Current Channel A and Current Channel B by setting the AVARACC and BVARACC bits to 10 in the ACCMODE register (Address 0x201 and Address 0x301). If enabled, the absolute accumulation mode affects both energy accumulation registers, RENERGYA and RENERGYB, as well as the CF output pins (see the Energy-to-Frequency Conversion section).

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ADE7953

This process occurs simultaneously on Current Channel A and Current Channel B, and the resulting readings can be read in the 24-bit APENERGYA (Address 0x222 and Address 0x322) and APENERGYB (Address 0x223 and Address 0x323) registers.

APPARENT POWER CALCULATION

Apparent power is defined as the maximum power that can be delivered to a load. VRMS and IRMS are the effective voltage and current delivered to the load, respectively. The apparent power can, therefore, be defined as the product of VRMS and IRMS. This relationship is independent of the phase angle between the voltage and current.

Note that the apparent energy register contents roll over to full-scale negative (0x800000) and continue to increase in value when the power or energy flow is positive. Conversely, if the Equation 26 provides an expression for the instantaneous

apparent power signal in an ac signal. power is negative, the energy register underflows to full-scale

positive (0x7FFFFF) and continues to decrease in value.

V(t) = 2×VRMS ×sin(ωt) (23)

APENERGYA and APENERGYB are read-with-reset registers

I(t) = 2×IRMS ×sin(ωt+θ) (24) by default. This means that the contents of these registers are

reset to 0 after a read operation. This feature can be disabled

P(t) = V(t) × I(t) (25)

by clearing Bit 6 (RSTREAD) of the LCYCMODE register

P(t) = VRMS × IRMS × cos(θ) − (26) (Address 0x004). VRMS × IRMS × cos(2ωt + θ)

The ADE7953 includes two sets of interrupts that are triggered

The ADE7953 computes the apparent power simultaneously when the apparent energy register is half full (positive or on Current Channel A and Current Channel B and stores the negative) or when an overflow or underflow condition occurs. resulting measurements in the AVA (Address 0x210 and The first set of interrupts is associated with the Current Address 0x310) and BVA (Address 0x211 and Address 0x311) Channel A apparent energy, and the second set of interrupts is registers, respectively. associated with the Current Channel B apparent energy. The apparent power measurement is taken over a bandwidth These interrupts are disabled by default and can be enabled by of 1.23 kHz and includes the effects of any harmonics within setting the VAEHFA and VAEOFA bits in the IRQENA register that range. The apparent power registers are updated at a rate of (Address 0x22C and Address 0x32C) for Current Channel A, 6.99 kHz and can be read using the waveform sampling mode and the VAEHFB and VAEOFB bits in the IRQENB register (see the Instantaneous Powers and Waveform Sampling section). (Address 0x22F and Address 0x32F) for Current Channel B.

APPARENT ENERGY CALCULATION

The apparent energy is given as the integral of the apparent power.

Apparent Energy Integration Time Under Steady Load

The discrete time sample period (T) for the accumulation registers is 4.76 μs (1/210 kHz). With full-scale sinusoidal signals on the analog inputs, a pulse is generated and added

Apparent Energy = ∫Apparent Power(t)dt (27)

to the APENERGYA and APENERGYB registers every 4.76 μs,

The ADE7953 achieves the integration of the apparent power assuming that the AVAGAIN and BVAGAIN registers are set signal in two stages. In the first stage, the apparent power to 0x00. The maximum positive value that can be stored in the signals are accumulated in an internal 48-bit register every 24-bit APENERGYA and APENERGYB registers is 0x7FFFFF 143 μs (6.99 kHz) until an internal fixed threshold is reached. before the register overflows. The integration time under these When this threshold is reached, a pulse is generated and is conditions can be calculated as follows: accumulated in 24-bit, user accessible accumulation registers. Time = 0x7FFFFF × 4.76 μs = 39.9 sec (28) The internal threshold results in a maximum accumulation rate

of approximately 210 kHz with full-scale inputs.

xVAGAINCURRENT RMSCHANNELA OR BVOLTAGERMSAPPARENTPOWERSIGNAL++48023APENERGYx0INTERNALACCUMULATIONFIXED INTERNALTHRESHOLD09320-024xVAOS

Figure 55. Apparent Energy Accumulation Signal Chain

Rev. 0 | Page 30 of 68

xVAGAINAPPARENTPOWERSIGNALxVAOS+480+INTERNALACCUMULATIONFIXED INTERNALTHRESHOLDADE7953

OUTPUT FROMVOLTAGE CHANNELADCLPF1ZERO-CROSSINGDETECTIONCALIBRATIONCONTROL23APENERGYx009320-12515LINECYC0

Figure 56. Apparent Energy Line Cycle Accumulation

Apparent Energy Line Cycle Accumulation Mode

In apparent energy line cycle accumulation mode, the energy accumulation of the ADE7953 is synchronized to the voltage channel zero crossing so that the apparent energy on Current Channel A and Current Channel B can be accumulated over an integral number of half line cycles. Line cycle accumulation mode is disabled by default and can be enabled on Current Channel A and Current Channel B by setting the ALVA and BLVA bits to 1 in the LCYCMODE register (Address 0x004). The accumulation time should be written to the LINECYC register (Address 0x101) in the unit of number of half line cycles. The number of half line cycles written to the LINECYC register is used for both the Current Channel A and Current Channel B accumulation periods. The ADE7953 can accumulate apparent energy for up to 65,535 half line cycles. This equates to an accu-mulation period of approximately 655 sec with 50 Hz inputs and 546 sec with 60 Hz inputs.

At the end of a line cycle accumulation cycle, the APENERGYA and APENERGYB registers are updated, and the CYCEND flag in the IRQSTATA register (Address 0x22D and Address 0x32D) is set. If the CYCEND bit in the IRQENA register is set, an external interrupt is issued on the IRQ pin. In this way, the IRQ pin can also be used to signal the completion of the line cycle accumula-tion. Another accumulation cycle begins immediately, as long as the ALVA and BLVA bits in the LCYCMODE register remain set. The contents of the APENERGYA and APENERGYB registers are updated synchronous to the CYCEND flag. The APENERGYA and APENERGYB registers hold their current values until the end of the next line cycle period, when the contents are replaced with the new reading. If the read-with-reset bit (RSTREAD) in the LCYCMODE register (Address 0x004) is set, the contents of the APENERGYA and APENERGYB registers are cleared after a read and remain at 0 until the end of the next line cycle period.

If a new value is written to the LINECYC register (Address 0x101) midway through a line cycle accumulation, the new value is not internally loaded until the end of a line cycle period. When the LINECYC register is updated mid-reading, the current energy accumulation cycle is completed, and the new value is then programmed, ready for the next cycle. This prevents any invalid readings due to changes to the LINECYC register (see Figure 47). Note that when line cycle accumulation mode is first enabled, the reading after the first CYCEND flag should be ignored because it may be inaccurate. This is because the line cycle accumulation mode is not synchronized to the zero crossing and, therefore, the first reading may not be over a complete number of half line cycles. After the first line cycle accumulation is complete, all successive readings will be correct.

AMPERE-HOUR ACCUMULATION

In a tampering situation where no voltage is available to the energy meter, the ADE7953 can accumulate the ampere-hour measure-ment instead of the apparent power in the APENERGYA and APENERGYB registers. If enabled, the Current Channel A and Current Channel B IRMS measurements are continually accu-mulated instead of the apparent power. If enabled, the apparent power CF output pin also reflects the ampere-hour measurement (see the Energy-to-Frequency Conversion section). All the signal processing and calibration registers available for the apparent power and apparent energy accumulation remain active when the ampere-hour accumulation mode is enabled. This includes the apparent energy no-load feature (see the Apparent Energy No-Load section). Recalibration is required in this mode due to internal scaling differences between the IRMS and apparent signals.

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ADE7953

The CF1 and CF2 pins can be configured to output a signal that is proportional to the active power, reactive power, apparent power, or IRMS on Current Channel A or Current Channel B. In addition, it is possible to configure CF1 and CF2 to output a signal that is proportional to the sum of the Current Channel A IRMS and the Current Channel B IRMS, or, alternatively, propor-tional to the sum of the active power on Current Channel A and the active power on Current Channel B. Recalibration is required in this configuration because the actual CF output equals the sum of the active power on Current Channel A and the active power on Current Channel B, divided by 2. The CF1 and CF2 output pins are programmed by setting the CF1SEL and CF2SEL bits in the CFMODE register (Address 0x107).

Both pulse outputs (CF1 and CF2) are disabled by default and can be enabled by clearing the CF1DIS and CF2DIS bits, respectively, in the CFMODE register (Address 0x107).

09320-026ENERGY-TO-FREQUENCY CONVERSION

The ADE7953 provides two energy-to-frequency conversions for calibration purposes. After initial calibration at manufacturing, the manufacturer or end customer is often required to verify the meter accuracy. One convenient way to do this is to provide an output frequency that is proportional to the active, reactive, or apparent power, or to the current rms under steady load condi-tions. This output frequency provides a simple single-wire interface that can be optically isolated to interface to external calibration equipment. The ADE7953 includes two fully

programmable calibration frequency output pins: CF1 (Pin 23) and CF2 (Pin 24). The energy-to-frequency conversion is illustrated in Figure 57.

CFxSEL BITSIN CFMODE REGISTER1VAIRMSVARWATTIRMSA + IRMSBAWATT + BWATTCFx PULSEOUTPUTDFC÷CFxDENPULSE OUTPUT CHARACTERISTICS

Figure 57. Energy-to-Frequency Conversion

Two digital-to-frequency converters (DFCs) are used to generate the pulse outputs. The DFC generates a pulse each time 1 LSB is accumulated in the energy register. An output pulse is generated when CFxDEN number of pulses is generated at the DFC output.

The pulse outputs for both DFCs stay low for 80 ms if the pulse period is longer than 160 ms (6.25 Hz). If the pulse period is shorter than 160 ms, the duty cycle of the pulse outputs is 50%. The pulse outputs are active low. The maximum output frequency with ac inputs at full scale and with CFxDEN = 0x00 is approxi-mately 210 kHz.

The ADE7953 includes two unsigned 16-bit registers, CF1DEN (Address 0x103) and CF2DEN (Address 0x104) that control the CF output frequency on the CF1 and CF2 pins, respectively. The 16-bit frequency scaling registers can scale the output frequency by 1/(216 – 1) to 1 with a step of 1/(216 – 1).

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ADE7953

Current Channel Gain Adjustment

A gain calibration register is also provided on Current Channel B. This register can be used to match Current Channel B to Current Channel A for simple calibration and computation. The Current Channel B gain calibration is performed using the BIGAIN register (Address 0x28C and Address 0x38C). Equation 32 shows the relationship between the gain adjustment and the IRMSB register.

ENERGY CALIBRATION

GAIN CALIBRATION

The active, reactive, and apparent power measurements can be calibrated on Current Channel A and Current Channel B separately. This allows meter-to-meter gain variation to be compensated for.

The AWGAIN register (Address 0x282 and Address 0x382) controls the active power gain calibration on Current Channel A, and the BWGAIN register (Address 0x28E and Address 0x38E) controls the active power gain calibration on Current Channel B. The default value of the xWGAIN registers is 0x400000, which corresponds to no gain calibration. The minimum value that can be written to the xWGAIN registers is 0x200000, which represents a gain adjustment of −50%. The maximum value that can be written to the xWGAIN registers is 0x600000, which represents a gain adjustment of +50%. Equation 29 shows the relationship between the gain adjustment and the xWGAIN registers.

IRMSB Expected =

⎛BIGAIN⎞

⎟ IRMSBINITIAL ×⎜

⎜0x400000⎟

⎠⎝

(32)

Similar registers are available for the voltage channel and for

Current Channel A. The VGAIN register (Address 0x281 and Address 0x381) and the AIGAIN register (Address 0x280 and Address 0x380) provide the calibration adjustment and function in the same way as the BIGAIN register.

Output Power (W) = ⎛xWGAIN⎞

⎟ Active Power ×⎜

⎜0x400000⎟

⎠⎝

(29) PHASE CALIBRATION

The ADE7953 is designed to function with a variety of current

transducers, including those that induce inherent phase errors. A phase error of 0.1° to 0.3° is not uncommon for a current transformer (CT). These phase errors can vary from part to part, and they must be corrected to achieve accurate power readings. The errors associated with phase mismatch are particularly noticeable at low power factors. The ADE7953 provides a means of digitally calibrating these small phase errors by introducing a time delay or a time advance.

Because different sensors can be used on Current Channel A and Current Channel B, separate phase calibration registers are included on each channel. The PHCALA register (Address 0x108) can be used to correct phase errors on Current Channel A, and the PHCALB register (Address 0x109) can be used to correct phase errors on Current Channel B. Both registers are in 10-bit sign magnitude format, with the MSB indicating whether a time delay or a time advance is added to the corresponding current channel. Writing a 0 to the MSB of the PHCALx register intro-duces a time delay to the current channel. Writing a 1 to the MSB of the PHCALx register introduces a time advance. The maximum range that can be written to PHCALx[8:0] is 383 (decimal). One LSB of the PHCALx register is equivalent to a time delay or time advance of 1.12 μs (CLKIN/4). With a line frequency of 50 Hz, the resolution is 0.02°/LSB ((360 × 50 Hz)/898.857 kHz), which provides a total correction of 7.66° in either direction. With a line frequency of 60 Hz, the resolution is 0.024°/LSB ((360 × 60 Hz)/898.857 kHz), which provides a total correction of 9.192° in either direction.

Similar gain calibration registers are available for the reactive power and the apparent power. The reactive power on Current Channel A and Current Channel B can be gain calibrated using the AVARGAIN (Address 0x283 and Address 0x383) and BVARGAIN (Address 0x28F and Address 0x38F) registers, respectively. The apparent power on Current Channel A and Current Channel B can be gain calibrated using the AVAGAIN (Address 0x284 and Address 0x384) and BVAGAIN

(Address 0x290 and Address 0x390) registers, respectively. The xVARGAIN and xVAGAIN registers affect the reactive and apparent powers in the same way that the xWGAIN registers affect the active power. Equation 29 can therefore be modified to represent the gain calibration of the reactive and apparent powers, as shown in Equation 30 and Equation 31.

Output Power (VAR) =

⎛xVARGAIN⎞

⎟ Reactive Power ×⎜

⎜0x400000⎟

⎠⎝

(30)

Output Power (VA) =

⎛xVAGAIN⎞⎟ Apparent Power ×⎜

⎜0x400000⎟

⎠⎝

(31)

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ADE7953

RMS Offsets

The ADE7953 includes offset calibration registers to allow offset in the rms measurements to be corrected. Offset cali-bration registers are available for the IRMS measurements on Current Channel A and Current Channel B, as well as for the VRMS measurement. Offset can exist in the rms calculation due to input noise that is integrated in the dc component of V2(t). The offset calibration allows these offsets to be removed to increase the accuracy of the measurement at low input levels. The voltage rms offset can be corrected by adjusting the VRMSOS register (Address 0x288 and Address 0x388). This 24-bit, signed twos complement register has a default value of 0, indicating that no offset is added. The VRMSOS value is applied prior to the square root function. Equation 33 shows the effect of the VRMSOS register on the VRMS measurement.

OFFSET CALIBRATION

Power Offsets

The ADE7953 includes offset calibration registers for the active, reactive, and apparent powers on Current Channel A and Current Channel B. Offsets can exist in the power calculations due to crosstalk between channels on the PCB and in the ADE7953. The offset calibration allows these offsets to be removed to increase the accuracy of the measurement at low input levels. The active power offset can be corrected on Current Channel A and Current Channel B by adjusting the AWATTOS (Address 0x289 and Address 0x389) and BWATTOS (Address 0x295 and Address 0x395) registers, respectively. The xWATTOS registers are 24-bit, signed twos complement registers with default values of 0. One LSB in the xWATTOS register is equivalent to 0.001953 LSBs in the active power measurement. The

xWATTOS value is, therefore, applied to the xWATT register, shifted by nine bits, as shown in Figure 58.

23xWATTOS90VRMS = VRMS02+VRMSOS × 212 (33) where VRMS0 is the initial VRMS reading prior to offset calibration.

The current rms offset is calibrated in a similar way. The AIRMSOS register (Address 0x286 and Address 0x386) compensates for offsets in the IRMSA measurement, and the BIRMSOS register (Address 0x292 and Address 0x392) compensates for offsets in the IRMSB measurement. Both registers are 24-bit, signed twos complement registers. The xIRMSOS registers affect the IRMS measurements in the same way that the VRMSOS register affects the VRMS measurement. Equation 33 can therefore be modified to represent the offset calibration on the IRMS, as shown in Equation 34 and Equation 35.

xWATT230

Figure 58. xWATTOS and xWATT Registers

With full-scale inputs on the voltage and current channels, the expected power reading is approximately 5,000,000 LSBs (deci-mal). At −60 dB (1000:1) on Current Channel A and Current Channel B, the expected readings in the AWATT and BWATT registers, respectively, are approximately 5000 (decimal). One LSB of the xWATT register, therefore, corresponds to 0.000039% at −60 dB.

The reactive power offset can be corrected on Current Channel A and Current Channel B by adjusting the AVAROS (Address 0x28A and Address 0x38A) and BVAROS (Address 0x296 and Address 0x396) registers, respectively. The xVAROS registers affect the reactive power in the same way that the xWATTOS registers affect the active power.

The apparent power offset can be corrected on Current Channel A and Current Channel B by adjusting the AVAOS (Address 0x28B and Address 0x38B) and BVAOS (Address 0x297 and Address 0x397) registers, respectively. The xVAOS registers affect the apparent power in the same way that the xWATTOS registers affect the active power.

09320-027IRMSA = IRMSA02+AIRMSOS × 212 (34)

IRMSB = IRMSB02+BIRMSOS × 212 (35)

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ADE7953

The value of the period register for a 50 Hz network is approxi-mately 4460 in decimal (223 kHz/50 Hz) and 3716 in decimal (223 kHz/60 Hz) for a 60 Hz network. The period register is stable at ±1 LSB when the line is established and the measure-ment does not change.

The following equation can be used to compute the line period and frequency using the period register:

PERIOD[15:0]+1

PERIOD MEASUREMENT

The ADE7953 provides a period measurement of the voltage channel. This measurement is provided in the 16-bit, unsigned period register (Address 0x10E). The period register is updated once every line period and has a settling time of 30 ms to 40 ms associated with it before the period measurement is stable. The period measurement has a resolution of 4.48 μs/LSB (223 kHz clock), which represents 0.0224% when the line frequency is 50 Hz and 0.0268% when the line frequency is 60 Hz.

TL=

223kHz

sec (36)

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ADE7953

Table 7. Waveform Sampling Registers

Address

easurement Register 24-Bit 32-Bit AWATT 0x212 0x312 Active power

(Current Channel A)

BWATT 0x213 0x313 Active power

(Current Channel B)

AVAR 0x214 0x314 Reactive power

(Current Channel A)

BVAR 0x215 0x315 Reactive power

(Current Channel B)

AVA 0x210 0x310 Apparent power

(Current Channel A)

BVA 0x211 0x311 Apparent power

(Current Channel B)

IA 0x216 0x316 Current

(Current Channel A)

IB 0x217 0x317 Current

(Current Channel B)

V 0x218 0x318 Voltage

(voltage channel)

INSTANTANEOUS POWERS AND WAVEFORM SAMPLING

The ADE7953 provides access to the current and voltage channel waveform data, along with the instantaneous active, reactive, and apparent powers. This information allows the instantaneous data to be analyzed in more detail, including reconstruction of the current and voltage input for harmonic analyses. These measurements are available from a set of 24-/32-bit signed registers (see Table 7).

All measurements are updated at a rate of 6.99 kHz (CLKIN/512). The ADE7953 provides an interrupt status bit, WSMP, that is triggered at a rate of 6.99 kHz, allowing measurements to be synchronized with the instantaneous signal update rate. This status bit is available in the IRQSTATA register (Address 0x22D and Address 0x32D). This signal can also be configured to trigger an interrupt on the external IRQ pin by setting the WSMP bit (Bit 17) in the IRQENA register (Address 0x22C and Address 0x32C).

The ADE7953 also provides the option of issuing an unlatched, data-ready signal at the same rate of 6.99 kHz. This signal provides the same information as the WSMP interrupt, but it is unlatched and, therefore, does not need to be serviced each time that new data is available. The data-ready signal goes high for a period of 280 ns before automatically returning low. The data-ready signal is disabled by default and can be output on the REVP, ZX, and ZX_I pins by setting the REVP_ALT, ZX_ALT, and ZXI_ALT bits to 1001 in the ALT_OUTPUT register (Address 0x110).

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By default, the instantaneous active and apparent power

readings are used to calculate the power factor, and the register is updated at a rate of 6.99 kHz. The sign bit is taken from the instantaneous reactive energy measurement on each channel.

POWER FACTOR

The ADE7953 provides a direct power factor measurement simultaneously on Current Channel A and Current Channel B. Power factor in an ac circuit is defined as the ratio of the active power flowing to the load to the apparent power. The power factor measurement is defined in terms of “leading” or “lagging,” referring to whether the current waveform is leading or lagging the voltage waveform.

When the current waveform is leading the voltage waveform, the load is capacitive and is defined as a negative power factor. When the current waveform is lagging the voltage waveform, the load is inductive and is defined as a positive power factor. The relationship of the current waveform to the voltage wave-form is illustrated in Figure 59.

ACTIVE (–)REACTIVE (–)IACTIVE (+)REACTIVE (–)CAPACITIVE LOAD:CURRENT LEADSVOLTAGEV–60° = θ; PF = +0.5INDUCTIVE LOAD:CURRENT LAGSVOLTAGEUSING THE LINE CYCLE ACCUMULATION MODE TO DETERMINE THE POWER FACTOR

If a power factor measurement with more averaging is required, the ADE7953 can use the line cycle accumulation measurement on the active and apparent energies to determine the power factor (see the Active Energy Line Cycle Accumulation Mode section and the Apparent Energy Line Cycle Accumulation Mode section). This option provides a more stable power factor reading. To use the line cycle accumulation mode to determine the power factor, the ADE7953 must be configured as follows: • •

The PFMODE bit (Bit 3) must be set to 1 in the CONFIG register (Address 0x102).

The line cycle accumulation mode must be enabled on both the active and apparent energies by setting the

xLWATT and xLVA bits to 1 in the LCYCMODE register (Address 0x004).

+60° = θ; PF = –0.5ACTIVE (–)REACTIVE (+)ACTIVE (+)REACTIVE (+)09320-028I

Figure 59. Capacitive and Inductive Loads

As shown in Figure 59, the reactive power measurement is negative when the load is capacitive and positive when the load is inductive. The sign of the reactive power can therefore be used to reflect the sign of the power factor.

The mathematical definition of power factor is shown in Equation 37.

Power Factor =

(SignofReactivePower)×

Active PowerApparent Power

(37)

When using line cycle accumulation to determine the power factor, the update rate of the power factor measurement is an integral number of half line cycles. The number of half line cycles is programmed in the LINECYC register (Address 0x101). For complete information about setting up the line cycle accumula-tion mode, see the Active Energy Line Cycle Accumulation Mode section and the Apparent Energy Line Cycle Accumulation Mode section.

POWER FACTOR WITH NO-LOAD DETECTION

The power factor measurement is affected by the no-load condition if no-load detection is enabled (see the No-Load Detection section). The following considerations apply only when no-load detection is enabled and a no-load condition occurs: •

If the apparent energy no-load condition is true, the power factor measurement is set to 1 because it is assumed that there is no active or reactive power.

If the active energy no-load condition is true, the power factor measurement is set to 0 because it is assumed that the load is purely capacitive or inductive.

If the reactive energy no-load condition is true, the sign of the power factor is based on the sign of the active power.

The power factor measurement includes the effect of all harmonics over the 1.23 kHz bandwidth.

The power factor readings are stored in two 16-bit, signed registers: PFA (Address 0x10A) for Current Channel A and PFB (Address 0x10B) for Current Channel B. These registers are signed, twos complement registers with the MSB indicating the polarity of the power factor. Each LSB of the PFx register equates to a weight of 2−15; therefore, the maximum register value of 0x7FFF corresponds to a power factor value of 1. The minimum register value of 0x8000 corresponds to a power factor of −1.

•

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ADE7953

The time delay between the current and voltage inputs can be used to characterize how balanced the load is. The delays between phase voltages and currents can be used to compute the power factor on Current Channel A and Current Channel B, respec-tively, as shown in Equation 38.

⎛360o×fLINE⎞

⎟ (38) cosφx=cos⎜ANGLE_x×

⎜⎟223kHz⎝⎠where:

x = A or B.

fLINE is 50 Hz or 60 Hz.

This method of determining the power factor does not take into account the effect of any harmonics. Therefore, it may not be equal to the true definition of power factor shown in Equation 37.

09320-031ANGLE MEASUREMENT

The ADE7953 can measure the time delay between the current and voltage inputs. This feature is available on both Current Channel A and Current Channel B. The negative-to-positive transitions identified by the zero-crossing detection circuit are used as a start and stop for the measurement (see Figure 60).

PHASE AVOLTAGEPHASE ACURRENTANGLE_x

Figure 60. Current-to-Voltage Time Delay

The ADE7953 provides a time delay measurement on Current Channel A and Current Channel B simultaneously. The result-ing measurements are available in the 16-bit, signed registers ANGLE_A (Address 0x10C) and ANGLE_B (Address 0x10D). One LSB of the ANGLE_A or ANGLE_B register corresponds to 4.47 μs (223 kHz clock). This results in a resolution of 0.0807° at 50 Hz ((360 × 50)/223 kHz) and 0.0969° at 60 Hz ((360 × 60)/223 kHz).

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ACTIVE ENERGY NO-LOAD DETECTION

Active energy no-load detection can be used in conjunction with reactive energy no-load detection to establish a “true” no-load feature. If both the active and reactive energy fall below the no-load threshold, there is no resistive, inductive, or capacitive load. The active energy no-load feature can also be used to prevent creep of the active energy when there is an inductive or capacitive load present.

NO-LOAD DETECTION

The ADE7953 includes a no-load detection feature that eliminates “meter creep.” Meter creep is defined as excess energy that is accumulated by the meter when there is no load attached. The ADE7953 warns of this condition and stops energy accumula-tion if the energy falls below a programmable threshold. The ADE7953 includes a no-load feature on the active, reactive, and apparent energy measurements. This allows a true no-load condition to be detected and also prevents creep in purely resistive, inductive, or capacitive load conditions. The no-load feature is enabled by default.

If the active energy on either Current Channel A (phase) or Current Channel B (neutral) falls below the programmed

SETTING THE NO-LOAD THRESHOLDS threshold, the active energy on that channel ceases to accumu-Three separate 24-/32-bit registers are available to set the late in the AENERGYA and AENERGYB registers, respectively. no-load threshold on the active, reactive, and apparent If either the CF1 or CF2 pin is programmed to output active energies: AP_NOLOAD (Address 0x203 and Address 0x303), energy, the CF output is disabled and held high (see the Energy-VAR_NOLOAD (Address 0x204 and Address 0x304), and to-Frequency Conversion section). If enabled, the active reverse VA_NOLOAD (Address 0x205 and Address 0x305). The active, power indication (REVP) holds its current state while in the no-reactive, and apparent energy no-load thresholds are completely load condition (see the Reverse Power section). The Current independent and, therefore, all three thresholds are required. Channel A active energy no-load condition is indicated by the The no-load thresholds for all three measurements can be set AP_NOLOADA bit (Bit 6) in the IRQSTATA register (Address based on Equation 39. 0x22D and Address 0x32D). The Current Channel B active energy

no-load condition is indicated by the AP_NOLOADB bit (Bit 6) Y

(39) X_NOLOAD = 65,536−in the IRQSTATB register (Address 0x230 and Address 0x330). 1.4where:

X is AP, VAR, or VA.

Y is the required threshold amplitude with reference to full-scale energy (for example 20,000:1).

As shown in Equation 39, the no-load threshold can be config-ured based on the required level with respect to full scale. For example, if a no-load threshold of 10,000:1 of the full-scale current channel is required and the voltage channel is set up to operate at ±250 mV (50% of full scale), then a value of 20,000 is required for Y. A default value of 58,393 (decimal) is programmed into the AP_NOLOAD and VAR_NOLOAD registers, setting the initial no-load threshold to approximately 10,000:1. The VA_NOLOAD register has a default value of 0x00.

The no-load thresholds AP_NOLOAD, VAR_NOLOAD, and VA_NOLOAD must be written before enabling the no-load feature. The no-load feature is enabled using the DISNOLOAD register (Address 0x001). If the threshold requires modification, disable the no-load detection, modify the threshold, and then reenable the feature using the DISNOLOAD register.

Although separate no-load interrupts are available for Current Channel A and Current Channel B (phase and neutral current), the same no-load level is used for both. For example, if the VAR_NOLOAD level is set to 0.05% of full scale, this value is the reactive power no-load threshold used for both Current Channel A (phase) and Current Channel B (neutral).

Current Channel A and Current Channel B are independent and, therefore, a no-load condition on Current Channel A affects only the energy accumulation, CF output, and reverse power of Current Channel A, and vice versa.

The active energy no-load feature is enabled by default and can be disabled by setting Bit 0 in the DISNOLOAD register (Address 0x001) to 1.

Active Energy No-Load Interrupt

Two interrupts are associated with the active energy no-load feature: one for Current Channel A (phase) and one for Current Channel B (neutral). If enabled, these interrupts are triggered when the active energy falls below the programmed threshold. The Current Channel A active energy no-load interrupt can be enabled by setting the AP_NOLOADA bit (Bit 6) in the IRQENA register (Address 0x22C and Address 0x32C). When this bit is set, an active energy no-load event on Current Channel A causes the IRQ pin (Pin 22) to fall to 0 (see the Primary Interrupts (Voltage Channel and Current Channel A) section).

The Current Channel B active energy no-load interrupt can be enabled by setting the AP_NOLOADB bit (Bit 6) in the IRQENB register (Address 0x22F and Address 0x32F). When this bit is set, an active energy no-load event on Current Channel B triggers the IRQ alternative output (see the Current Channel B Interrupts section).

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ADE7953

The Current Channel B reactive energy no-load interrupt can be enabled by setting the VAR_NOLOADB bit (Bit 7) in the IRQENB register (Address 0x22F and Address 0x32F). When this bit is set, a reactive power no-load event on Current Channel B triggers the IRQ alternative output (see the Current Channel B Interrupts section).

Active Energy No-Load Status Bits

In addition to the active energy no-load interrupt, the ADE7953 includes two unlatched status bits that continually monitor the no-load status of Current Channel A and Current Channel B. The ACTNLOAD_A and ACTNLOAD_B bits are located in the ACCMODE register (Address 0x201 and Address 0x301). These bits differ from the interrupt status bits in that they are unlatched and can, therefore, be used to drive an LED.

Reactive Energy No-Load Status Bits

In addition to the reactive energy no-load interrupt, the ADE7953 includes two unlatched status bits that continually monitor the no-load status of Current Channel A and Current Channel B. The VARNLOAD_A and VARNLOAD_B bits are located in the ACCMODE register (Address 0x201 and Address 0x301). These bits differ from the interrupt status bits in that they are unlatched and can, therefore, be used to drive an LED.

REACTIVE ENERGY NO-LOAD DETECTION

Reactive energy no-load detection can be used in conjunction with active energy no-load detection to establish a “true” no-load feature. If both the reactive and active energy fall below the no-load threshold, there is no resistive, inductive, or capacitive load. The reactive energy no-load feature can also be used to prevent creep of the reactive energy when there is a resistive load present. If the reactive energy on either Current Channel A (phase) or Current Channel B (neutral) falls below the programmed thresh-old, the reactive energy on that channel ceases to accumulate in the RENERGYA and RENERGYB registers, respectively. If either the CF1 or CF2 pin is programmed to output reactive energy, the CF output is disabled and held high (see the Energy-to-Frequency Conversion section). If enabled, the reactive reverse power indi-cation holds its current state while in the no-load condition (see the Reverse Power section). The Current Channel A reactive energy no-load condition is indicated by the VAR_NOLOADA bit (Bit 7) in the IRQSTATA register (Address 0x22D and Address 0x32D). The Current Channel B reactive energy no-load condition is indicated by the VAR_NOLOADB bit (Bit 7) in the IRQSTATB register (Address 0x230 and Address 0x330). Current Channel A and Current Channel B are independent and, therefore, a no-load condition on Current Channel A affects only the energy accumulation, CF output, and reverse power of Current Channel A, and vice versa.

The reactive energy no-load feature is enabled by default and can be disabled by setting Bit 1 in the DISNOLOAD register (Address 0x001) to 1.

APPARENT ENERGY NO-LOAD DETECTION

Apparent energy no-load detection can be used to determine whether the total consumed energy is below the no-load thresh-old. If the apparent energy on either Current Channel A (phase) or Current Channel B (neutral) falls below the programmed threshold, the apparent energy on that channel ceases to

accumulate in the APENERGYA and APENERGYB registers, respectively. If either the CF1 or CF2 pin is programmed to output apparent energy, the CF output is disabled and held high (see the Energy-to-Frequency Conversion section). The Current Channel A apparent energy no-load condition is indicated by the VA_NOLOADA bit (Bit 8) in the IRQSTATA register (Address 0x22D and Address 0x32D). The Current Channel B apparent energy no-load condition is indicated by the VA_NOLOADB bit (Bit 8) in the IRQSTATB register (Address 0x230 and Address 0x330).

Current Channel A and Current Channel B are independent and, therefore, a no-load condition on Current Channel A affects only the energy accumulation and CF output of Current Channel A, and vice versa.

The apparent energy no-load feature is enabled by default and can be disabled by setting Bit 2 in the DISNOLOAD register (Address 0x001) to 1.

Reactive Energy No-Load Interrupt

Two interrupts are associated with the reactive energy no-load feature: one for Current Channel A (phase) and one for Current Channel B (neutral). If enabled, these interrupts are triggered when the reactive energy falls below the programmed threshold. The Current Channel A reactive energy no-load interrupt can be enabled by setting the VAR_NOLOADA bit (Bit 7) in the IRQENA register (Address 0x22C and Address 0x32C). When this bit is set, a reactive energy no-load event on Current Channel A causes the IRQ pin (Pin 22) to fall to 0 (see the Primary Interrupts (Voltage Channel and Current Channel A) section).

Apparent Energy No-Load Interrupt

Two interrupts are associated with the apparent energy no-load feature: one for Current Channel A (phase) and one for Current Channel B (neutral). If enabled, these interrupts are triggered when the apparent energy falls below the programmed threshold. The Current Channel A apparent energy no-load interrupt can be enabled by setting the VA_NOLOADA bit (Bit 8) in the IRQENA register (Address 0x22C and Address 0x32C). When this bit is set, an apparent energy no-load event on Current Channel A causes the IRQ pin (Pin 22) to fall to 0 (see the Primary Interrupts (Voltage Channel and Current Channel A) section).

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ADE7953

Apparent Energy No-Load Status Bits

In addition to the apparent energy no-load interrupt, the ADE7953 includes two unlatched status bits that continually monitor the no-load status of Current Channel A and Current Channel B. The VANLOAD_A and VANLOAD_B bits are located in the ACCMODE register (Address 0x201 and Address 0x301). These bits differ from the interrupt status bits in that they are unlatched and can, therefore, be used to drive an LED.

The Current Channel B apparent energy no-load interrupt can be enabled by setting the VA_NOLOADB bit (Bit 8) in the IRQBENB register (Address 0x22F and Address 0x32F). When this bit is set, an apparent energy no-load event on Current Channel B triggers the IRQ alternative output (see the Current Channel B Interrupts section).

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ADE7953

As shown in Figure 62, the ZX output pin goes high on the positive-going edge of the voltage channel zero crossing and low on the negative-going edge of the zero crossing. A delay of approximately 2.2 ms should be expected on this pin due to the time delay of LPF1.

ZERO-CROSSING DETECTION

The ADE7953 includes a zero-crossing (ZX) detection feature on all three input channels. Zero-crossing detection allows measurements to be synchronized to the frequency of the incoming waveforms.

Zero-crossing detection is performed at the output of LPF1 to ensure that no harmonics or distortion affect the accuracy of the zero-crossing measurement. LPF1 is a single-pole filter with a −3 dB cutoff of 80 Hz and is clocked at 223 kHz. The phase shift of this filter therefore results in a time delay of approximately 2.2 ms (39.6°) at 50 Hz. To assure good resolution of the ZX detection, LPF1 cannot be disabled. Figure 61 shows how the zero-crossing signal is detected.

DSPREFERENCEIA, IB,OR VPGAADCGAIN[23:0]HPFEN BITZXDETECTIONHPFLPF1Current Channel Zero Crossing

The current channel zero-crossing indicator is output on Pin 21 (ZX_I) by default. The ZX_I pin operates in a similar way to the ZX pin (see Figure 62). The ZX_I pin goes high on the positive-going edge of the current channel zero crossing and low on the negative-going edge of the current channel zero crossing. By default, the ZX_I pin is triggered based on Current Channel A. The ZX_I pin can be configured to trigger based on Current Channel B by setting the ZX_I bit (Bit 11) of the CONFIG register (Address 0x102) to 1.

ZERO-CROSSING INTERRUPTS

Three interrupts are associated with zero-crossing detection, one for each input channel: Current Channel A, Current Channel B, and the voltage channel. The zero-crossing condition occurs when either a positive or a negative zero-crossing transition takes place. If this transition occurs on the voltage channel, the ZXV bit (Bit 15) of the IRQSTATA register (Address 0x22D and Address 0x32D) is set to 1. If this transition occurs on Current Channel A, the ZXIA bit (Bit 12) of the IRQSTATA register is set to 1. If this transition occurs on Current Channel B, the ZXIB bit (Bit 12) of the IRQSTATB register (Address 0x230 and Address 0x330) is set to 1. Figure 63 shows the operation of the voltage channel zero-crossing interrupt.

VZXV (BIT 15) OFIRQSTATA REGISTER39.6° OR 2.2ms @ 50Hz0VIA, IB, OR VZXZXZXZXLPF1 OUTPUT09320-127

Figure 61. Zero-Crossing Detection

The error in the ZX detection is 0.08° for 50 Hz systems and 0.09° for 60 Hz systems. The zero-crossing information is available on both an output pin or via an interrupt.

ZERO-CROSSING OUTPUT PINS

By default, the voltage and current channel ZX information is configured to be output on Pin 1 (ZX) and Pin 21 (ZX_I),

respectively. These dedicated output pins provide an unlatched ZX indicator (see the Alternative Output Functions section).

Voltage Channel Zero Crossing

The voltage channel zero-crossing indicator is output on Pin 1 (ZX) by default. Figure 62 shows the operation of the ZX output.

V2.2ms @ 50Hz09320-032

Figure 63. Zero-Crossing Interrupt

Figure 62. Voltage Channel ZX Output

As shown by the dotted line in Figure 63, the ADE7953 can be configured to trigger a zero-crossing event on only the positive-going or the negative-going zero crossing. The ZX_EDGE bits (Bits[13:12]) of the CONFIG register (Address 0x102) set the edge that triggers the zero-crossing event. These bits default to 00 (the zero-crossing event is triggered on both the positive-going and negative-going edges). Changing the ZX_EDGE bits affects the zero-crossing event on all three channels. Note that changing the ZX_EDGE bits affects only the ZX status bits and interrupts; the function of the ZX pin (Pin 1) and the ZX_I pin (Pin 21) is not affected.

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ADE7953

ZXTOUTADDRESS 0x100A zero-crossing event on any of the three input channels can be configured to trigger an external interrupt. All zero-crossing external interrupts are disabled by default. The voltage channel zero-crossing interrupt is enabled by setting the ZXV bit (Bit 15) in the IRQENA register (Address 0x22C and Address 0x32C). If this bit is set, a voltage channel zero-crossing event causes the IRQ pin to go low. The Current Channel A zero-crossing interrupt is enabled by setting the ZXIA bit (Bit 12) in the IRQENA register (Address 0x22C and Address 0x32C). If this bit is set, a Current Channel A zero-crossing event causes the IRQ pin to go low. The Current Channel B zero-crossing interrupt is enabled by setting the ZXIB bit (Bit 12) in the IRQENB register (Address 0x22F and Address 0x32F). If this bit is set, a Current Channel B zero-crossing event causes the IRQ pin to go low (see the ADE7953 Interrupts section).

INPUTSIGNALZXTO_x09320-033

Figure 64. Zero-Crossing Timeout

ZERO-CROSSING TIMEOUT

The ADE7953 includes a zero-crossing timeout feature that is designed to detect when no zero crossings are obtained over a programmable time period. This feature is available on both current channels and the voltage channel and can be used to detect when the input signal has dropped out. The duration of the zero-crossing timeout is programmed in the 16-bit ZXTOUT register (Address 0x100). The same timeout duration is used for all three channels. The value in the ZXTOUT register is decre-mented by 1 LSB every 14 kHz (CLKIN/256). If a zero crossing is obtained, the ZXTOUT register is reloaded. If the ZXTOUT register reaches 0, a zero-crossing timeout event is issued. The ZXTOUT register has a resolution of 0.07 ms (1/14 kHz); there-fore, the maximum programmable timeout period is 4.58 seconds. As shown in Figure 64, a zero-crossing event causes one of the zero-crossing timeout bits—ZXTO, ZXTO_IA, or ZXTO_IB—to be set to 1. The ZXTO and ZXTO_IA bits are located in the IRQSTATA register (Address 0x22D and Address 0x32D) and are set when a zero-crossing timeout event occurs on the voltage channel or on Current Channel A, respectively. The ZXTO_IB bit is located in the IRQSTATB register (Address 0x230 and Address 0x330) and is set when a zero-crossing timeout event occurs on Current Channel B.

Three interrupts are associated with the zero-crossing timeout feature. If enabled, a zero-crossing timeout event causes the external IRQ pin to go low. The interrupt associated with the voltage channel zero-crossing timeout can be enabled by setting the ZXTO bit (Bit 14) of the IRQENA register (Address 0x22C and Address 0x32C). The Current Channel A interrupt can be enabled by setting the ZXTO_IA bit (Bit 11) of the IRQENA register (Address 0x22C and Address 0x32C), and the Current Channel B interrupt can be enabled by setting the ZXTO_IB bit (Bit 11) of the IRQENB register (Address 0x22F and Address 0x32F). All three interrupts are disabled by default (see the ADE7953 Interrupts section).

ZERO-CROSSING THRESHOLD

To prevent spurious zero crossings when a very small input is present, an internal threshold is included on all channels of the ADE7953. This fixed threshold is set to a range of 1250:1 of the input full scale. If any input signal falls below this level, no zero-crossing signals are produced by the ADE7953 because they can be assumed to be noise. This threshold affects both the external zero-crossing pins, ZX (Pin 1) and ZX_I (Pin 21), as well as the zero-crossing interrupt function. At inputs of lower than 1250:1 of the full scale, the zero-crossing timeout signal continues to function and issues an event according to the time duration programmed in the ZXTOUT register (Address 0x100).

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If the SAGCYC value is modified after the feature is enabled, the new SAGCYC period is effective immediately. Therefore, it is possible for a sag event to be caused by a combination of sag cycle periods. To prevent any overlap, the SAGLVL register should be reset to 0 to effectively disable the feature before the new cycle value is written to the SAGCYC register.

VOLTAGE SAG DETECTION

The ADE7953 includes a sag detection feature that warns the user when the absolute value of the line voltage falls below the programmable threshold for a programmable number of line cycles. This feature can provide an early warning signal that the line voltage is dropping out. The voltage sag feature is controlled by two registers: SAGCYC (Address 0x000) and SAGLVL (Address 0x200 and Address 0x300). These registers control the sag period and the sag voltage threshold, respectively. Sag detection is disabled by default and can be enabled by writing a nonzero value to both the SAGCYC and SAGLVL registers. If either register is set to 0, the sag feature is disabled. If a voltage sag condition occurs, the sag bit (Bit 19) in the IRQSTATA register (Address 0x22D and Address 0x32D) and in the RSTIRQSTATA register (Address 0x22E and Address 0x32E) is set to 1.

SETTING THE SAGLVL REGISTER

The 24-/32-bit SAGLVL register contains the amplitude that the voltage channel must fall below before a sag event occurs. Each LSB of this register maps exactly to the voltage channel peak register; therefore, the amplitude can be set based on the peak reading of the voltage channel. To set the SAGLVL register,

nominal voltage should be applied and a reading taken from the RSTVPEAK register (Address 0x227 and Address 0x327) to reset the peak level reading. After a wait period of a few line cycles, the VPEAK register (Address 0x226 and Address 0x326) should be read to determine the voltage input. This reading should then be scaled to the amplitude required for sag detection. For example, if a sag threshold of 80% of the nominal voltage is required, the peak reading should be taken and a value of 80% of this reading should be written to the SAGLVL register. This method ensures that an accurate SAGLVL value is obtained for the particular design.

SETTING THE SAGCYC REGISTER

The 8-bit, unsigned SAGCYC register contains the program-mable sag period. The sag period is the number of half line cycles below which the voltage channel must remain before a sag condition occurs. Each LSB of the SAGCYC register

corresponds to one half line cycle period. The SAGCYC register holds a maximum value of 255.

At 50 Hz, the maximum sag cycle time is 2.55 seconds.

⎛1÷2⎞×255=2.55sec ⎜⎟⎝50⎠

At 60 Hz, the maximum sag cycle time is 2.125 seconds.

⎛1÷2⎞×255=2.125sec ⎜⎟⎝60⎠

VOLTAGE SAG INTERRUPT

The ADE7953 includes an interrupt that is associated with the voltage sag detection feature. If this interrupt is enabled, a voltage sag event causes the external IRQ pin to go low. This interrupt is disabled by default and can be enabled by setting the sag bit (Bit 19) in the IRQENA register (Address 0x22C and Address 0x32C). See the ADE7953 Interrupts section.

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These three registers are updated every time that the absolute value of the waveform exceeds the current value stored in the IAPEAK, IBPEAK, and VPEAK registers. No time period is associated with this measurement.

Three additional registers contain the same peak information, but cause the corresponding peak measurements to be reset after they are read. The three read-with-reset peak registers are RSTIAPEAK (Address 0x229 and Address 0x329), RSTIBPEAK (Address 0x22B and Address 0x32B), and RSTVPEAK (Address 0x227 and Address 0x327). Reading these registers clears the contents of the corresponding xPEAK register.

PEAK DETECTION

The ADE7953 includes a peak detection feature on both Current Channel A (phase) and Current Channel B (neutral) and on the voltage channel. This feature continuously records the maximum value of the voltage and current waveforms. Peak detection can be used with overvoltage and overcurrent detection to provide a complete swell detection function (see the Overcurrent and Overvoltage Detection section). Peak detection is an instantaneous measurement taken from the absolute value of the current and voltage ADC output waveforms and stored in three 24-/32-bit registers. The three registers that record the peak values on Current Channel A, Current Channel B, and the voltage channel, respectively, are IAPEAK (Address 0x228 and Address 0x328), IBPEAK

(Address 0x22A and Address 0x32A), and VPEAK (Address 0x226 and Address 0x326).

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This pulse has a 50% duty cycle. Similar to normal mode, this mode is also unlatched, and the REVP output returns high when the reverse polarity is no longer true. To enable the REVP pulse mode, the REVP_PULSE bit in the CONFIG register (Address 0x102) should be set to 1.

The REVP output pin is disabled in the corresponding no-load condition. For example, if the reverse polarity information for Current Channel A active power is present on the REVP pin and the active energy on Current Channel A is in the no-load condition, the REVP output is disabled and held in its current state.

INDICATION OF POWER DIRECTION

The ADE7953 includes sign indication on the active and reactive energy measurements. Sign indication allows positive and nega-tive energy to be identified and billed separately if required. It also helps detect a miswiring condition. This feature is available on both Current Channel A and Current Channel B. Power direction information is available on both a dedicated output pin (REVP) and via a set of internal registers and interrupts (see the Reverse Power section and the Sign Indication section).

REVERSE POWER

The REVP pin (Pin 20) on the ADE7953 provides a reverse power indicator. This pin can be configured to provide polarity information about the active or reactive power on Current Channel A or Current Channel B. The REVP output is high by default and goes low if the angle between the voltage and current input is greater than 90°. REVP is unlatched and, therefore, returns high when the reverse power condition is no longer true. Changes to the REVP output pin occur synchronously to the falling edge of the CF1 pin by default (see Figure 65). The measurement and channel indicated by the REVP pin are selected by the configuration of the CF output. By default, the REVP pin is configured to output synchronous to CF1 and represents the measurement selected on CF1 using the CF1SEL bits in the CFMODE register (Address 0x107). By default, this measurement is the active power on Current Channel A. If the CF1SEL bits are set to 0x0001, the REVP pin indicates the polarity of the reactive power on Current Channel A. The REVP indicator can be configured to output based on CF2 by setting the REVP_CF bit in the CONFIG register (Address 0x102). In this configura-tion, the CF2SEL bits in the CFMODE register determine the measurement represented on the REVP output. If the selected CF pin is configured to output another measurement, such as apparent power or IRMS, the REVP output is disabled. To improve the visibility of a reverse polarity condition if an LED light is used, a 1 Hz pulse mode is available on the REVP pin. In this mode, the REVP output pin is low by default and outputs a 1 Hz pulse if the reverse polarity condition is true.

ENTERREVERSECONDITIONREVPLOWSIGN INDICATION

The ADE7953 includes four sign indication bits that indicate the polarity of the active power on Current Channel A (APSIGN_A), the active power on Current Channel B (APSIGN_B), the reactive power on Current Channel A (VARSIGN_A), and the reactive power on Current Channel B (VARSIGN_B). These bits are located in the ACCMODE register (Address 0x201 and Address 0x301). All three bits are unlatched and read only. A low reading (0) on any of these bits indicates that the correspond-ing power reading is positive; a high reading (1) indicates that the corresponding power reading is negative. These bits are enabled by default and are disabled in the corresponding no-load condition.

In addition to the sign indication bits, the ADE7953 also includes four sign indication interrupts. If enabled, these interrupts cause the IRQ pin to go low when the polarity of the power changes. The interrupts are triggered on both positive-to-negative and negative-to-positive polarity changes. These interrupts are dis-abled by default and can be enabled by setting the APSIGN_A and VARSIGN_A bits in the IRQENA register (Address 0x22C and Address 0x32C), and the APSIGN_B and VARSIGN_B bits in the IRQENB register (Address 0x22F and Address 0x32F). See the ADE7953 Interrupts section.

Note that in absolute or positive-only accumulation mode, these bits are fixed at 0. See the Active Energy Accumulation Modes section and the Reactive Energy Accumulation Modes section.

EXITREVERSECONDITIONREVPHIGHCF1CURRENTANDVOLTAGEINPUTSREVP09320-034

Figure 65. REVP Output

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As shown in Figure 67, if an overcurrent condition is detected on Current Channel A, the OIA bit (Bit 13) of the IRQSTATA register is set to 1. This bit can be cleared by reading from the RSTIRQSTATA register. If an overcurrent condition is detected on Current Channel B, the OIB bit (Bit 13) of the IRQSTATB register (Address 0x230 and Address 0x330) is set to 1. This bit can be cleared by reading from the RSTIRQSTATB register (Address 0x231 and Address 0x331).

OVERCURRENT AND OVERVOLTAGE DETECTION

The ADE7953 provides an overcurrent and overvoltage feature that detects whether the absolute value of the current or voltage waveform exceeds a programmable threshold. This feature uses the instantaneous voltage and current signals. The two registers associated with this feature, OVLVL (Address 0x224 and

Address 0x324) and OILVL (Address 0x225 and Address 0x325), are used to set the voltage and current channel thresholds, respec-tively. The OILVL threshold register determines the threshold for both the Current Channel A and Current Channel B over-current features. The same threshold must therefore be used for both Current Channel A and Current Channel B. The default value of the OVLVL and OILVL registers is 0xFFFFFF, which effectively disables the feature. Figure 66 shows the operation of the overvoltage detection feature.

VOVLVLSETTING THE OVLVL AND OILVL REGISTERS

The 24-/32-bit unsigned OVLVL and OILVL registers map directly to the VPEAK (Address 0x226 and Address 0x326) and IAPEAK (Address 0x228 and Address 0x328) registers, respectively (see the Peak Detection section). Note that after gain calibration, Current Channel A and Current Channel B are matched and, therefore, the IAPEAK and IBPEAK registers are matched with common inputs. The settings of the OVLVL and OILVL registers should be based on the VPEAK and IAPEAK readings with full-scale inputs.

To set the OVLVL register, the maximum voltage input should be applied and a reading taken from the RSTVPEAK register (Address 0x227 and Address 0x327). This resets the voltage peak reading. After a wait period of a few line cycles, the VPEAK register (Address 0x226 and Address 0x326) should be read to determine the voltage peak. This reading should then be scaled to the amplitude required for overvoltage detection. For example, if an overvoltage threshold of 120% of the maximum voltage is required, the peak reading should be multiplied by 1.2 and the resulting value written to the OVLVL register. This method ensures that an accurate threshold is set for each individual design.

OV (BIT 16) OFIRQSTATA REGISTER09320-035OV RESETLOW WHENRSTIRQSTATAREGISTERIS READ

Figure 66. Overvoltage Detection

As shown in Figure 66, if the ADE7953 detects an overvoltage condition, the OV bit (Bit 16) of the IRQSTATA register

(Address 0x22D and Address 0x32D) is set to 1. This bit can be cleared by reading the RSTIRQSTATA register (Address 0x22E and Address 0x32E). The overcurrent detection feature works in a similar manner (see Figure 67).

IAOILVLOVERVOLTAGE AND OVERCURRENT INTERRUPTS

Three interrupts are associated with the overvoltage and

overcurrent features. The first interrupt is associated with the overvoltage feature; it is enabled by setting the OV bit (Bit 16) of the IRQENA register (Address 0x22C and Address 0x32C). When this bit is set, an overvoltage condition causes the external IRQ pin to be pulled low.

OIA (BIT 13) OFIRQSTATAREGISTERIBOILVLOIA RESET LOWWHEN RSTIRQSTATAREGISTER IS READA second interrupt is associated with the overcurrent detection feature on Current Channel A. This interrupt is enabled by setting the OIA bit (Bit 13) of the IRQENA register. When this bit is set, an overcurrent condition on Current Channel A causes the external IRQ pin to be pulled low.

The third interrupt is associated with the overcurrent detection feature on Current Channel B. This interrupt is enabled by setting the OIB bit (Bit 13) of the IRQENB register (Address 0x22F and Address 0x32F). When this bit is set, an overcurrent condition on Current Channel B causes the IRQ alternative output to be triggered, if the alternative output is enabled (see the Current Channel B Interrupts section).

Figure 67. Overcurrent Detection

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Table 8. Alternative Outputs

Function See This Section

Voltage Channel Zero CrossingZero-crossing detection

(voltage channel)

Current Channel Zero CrossingZero-crossing detection

(current channels)

Reverse power indication Reverse PowerVoltage sag detection Voltage Sag DetectionActive energy no-load Active Energy No-Load detection (Current Channel A) DetectionActive energy no-load Active Energy No-Load detection (Current Channel B) DetectionReactive energy no-load Reactive Energy No-Load detection (Current Channel A) DetectionReactive energy no-load Reactive Energy No-Load detection (Current Channel B) Detection

Waveform sampling, data ready Instantaneous Powers and

Waveform Sampling

Current Channel B InterruptsInterrupt output (Current

Channel B)

ALTERNATIVE OUTPUT FUNCTIONS

The ADE7953 includes three output pins that are configured by default to output power quality information. • •

Pin 1 (ZX) provides a voltage channel zero-crossing signal, as described in the Voltage Channel Zero Crossing section. Pin 21 (ZX_I) provides a current channel zero-crossing signal, as described in the Current Channel Zero Crossing section.

Pin 20 (REVP) provides polarity information, as described in the Reverse Power section.

•

To provide flexibility and to accommodate a variety of design requirements, the ADE7953 can be configured to output a variety of alternative power quality signals on any of these three outputs. Alternative functions are configured using the ALT_OUTPUT register (Address 0x110).

Table 8 summarizes the functions that can be output on Pin 1, Pin 21, and Pin 20. Note that the default functions of ZX, ZX_I, and REVP can be configured to output on any one of Pin 1, Pin 21, or Pin 20.

As described in Table 8, the description of each function can be found in the corresponding section of this data sheet. If an alter-native output function is enabled on Pin 1, Pin 21, or Pin 20, the function can be configured and will be performed as described in the corresponding section. The alternative function will, how-ever, appear as an unlatched output on Pin 1, Pin 21, or Pin 20. To enable an alternative function, the ZX_ALT, ZXI_ALT, and REVP_ALT bits in the ALT_OUTPUT register must be set. The interrupt enable associated with the alternative output does not need to be enabled in order for it to be present on Pin 1, Pin 21, or Pin 20. Enabling an alternative output does not affect the primary function of the feature.

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register, but when the RSTIRQSTATA register is accessed, a read-with-reset command is executed, clearing the status bits. After completion of a read from this register, all status bits are cleared to 0 and the IRQ pin returns to Logic 1.

ADE7953 INTERRUPTS

The ADE7953 interrupts are separated into two groups. The first group of interrupts is associated with the voltage channel and Current Channel A. The second group of interrupts is associated with Current Channel B. See Table 22 and Table 23 for a list of the interrupts.

All interrupts are disabled by default with the exception of the RESET interrupt that is located within the group of primary interrupts. This interrupt is enabled by default and signals the end of a software or hardware reset. On power-up, this interrupt is triggered to signal that the ADE7953 is ready to receive

communication from the microcontroller. This interrupt should be serviced as described in the Primary Interrupts (Voltage Channel and Current Channel A) section prior to configuring the ADE7953.

CURRENT CHANNEL B INTERRUPTS

The Current Channel B interrupts are events that occur on Current Channel B. Like the primary group of interrupts, Current Channel B interrupts are handled by a group of three registers: the enable register, IRQENB (Address 0x22F and Address 0x32F), the status register, IRQSTATB (Address 0x230 and Address 0x330), and the reset status register, RSTIRQSTATB (Address 0x231 and Address 0x331). The bits in these registers are described in Table 23.

When an interrupt event occurs, the corresponding bit in the IRQSTATB register is set to 1. The Current Channel B interrupts do not have a dedicated output pin. This function can be configured as an alternative output on Pin 1 (ZX), Pin 21 (ZX_I), or Pin 20 (REVP) (see the Alternative Output Functions section). If an output is enabled for interrupt events on Current Channel B and the interrupt enable bit, located in the IRQENB register, is set to 1, Pin 1, Pin 21, or Pin 20 is pulled low if an interrupt event occurs on Current Channel B. The status bits located in the IRQSTATB register are set when an interrupt event occurs, regardless of whether an external interrupt output is enabled.

All interrupts are latched and require servicing to clear. To service the interrupt, the status bits must be cleared using the RSTIRQSTATB register (Address 0x231 and Address 0x331). The RSTIRQSTATB register contains the same interrupt status bits as the IRQSTATB register, but when the RSTIRQSTATB register is accessed, a read-with-reset command is executed, clearing the status bits. After completion of a read from this register, all status bits are cleared to 0 and the appropriate output pin (if enabled) returns to Logic 1.

PRIMARY INTERRUPTS (VOLTAGE CHANNEL AND CURRENT CHANNEL A)

The primary interrupts are events that occur on the voltage channel and Current Channel A. These interrupts are handled by a group of three registers: the enable register, IRQENA (Address 0x22C and Address 0x32C), the status register, IRQSTATA (Address 0x22D and Address 0x32D), and the reset status register, RSTIRQSTATA (Address 0x22E and Address 0x32E). The bits in these registers are described in Table 22.

When an interrupt event occurs, the corresponding bit in the IRQSTATA register is set to 1. If the enable bit for this interrupt, located in the IRQENA register, is set to 1, the external IRQ pin is pulled to Logic 0. The status bits located in the IRQSTATA register are set when an interrupt event occurs, regardless of whether the external interrupt is enabled.

All interrupts are latched and require servicing to clear. To service the interrupt and return the IRQ pin to Logic 1, the status bits must be cleared using the RSTIRQSTATA register (Address 0x22E and Address 0x32E). The RSTIRQSTATA register contains the same interrupt status bits as the IRQSTATA

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Therefore, although Pin 25 (SCLK) and Pin 28 (CS) are not required if communicating via I2C or UART, these pins should be configured in hardware as shown in Table 9 to ensure the functionality of the autodetection system.

COMMUNICATING WITH THE ADE7953

All ADE7953 features can be accessed via a group of on-chip registers. For a detailed list of all the registers, see the ADE7953 Registers section. Three different communication interfaces can be used to access the on-chip registers. • • •

4-pin SPI interface

2-pin bidirectional I2C interface 2-pin UART interface

LOCKING THE COMMUNICATION INTERFACE

After the selected communication interface is established, the interface should be locked to prevent the communication method from inadvertently changing. The ADE7953 can be configured to lock automatically after the first successful communication.

The automatic lock feature is disabled by default and is enabled by clearing the COMM_LOCK bit (Bit 15) in the CONFIG register (Address 0x102). To successfully establish and lock the communication interface, a write should be issued shortly after power-up to the CONFIG register, clearing the COMM_LOCK bit and thus locking the communication interface. When the communication interface is locked to a specific method (that is, SPI, I2C, or UART), the communication method cannot be changed without resetting the ADE7953.

Note that if using the SPI communication interface to lock the communication mode, the CS pin must be held low for a minimum of 1.2 μs after the last SCLK. This delay is required only when writing to the COMM_LOCK bit (see the SPI Interface Timing section).

All three communication options use the same group of pins and, therefore, only one method of communication should be used in each design.

COMMUNICATION AUTODETECTION

The ADE7953 contains a detection system that automatically detects which of the three communication interfaces is being used. This feature allows communication to be quickly estab-lished with minimal initialization. Autodetection works by monitoring the status of the four communication pins and automatically selecting the communication interface that matches the configuration (see Table 9). •

The CS pin (Pin 28) is used to determine whether the communication method is SPI. If this pin is held low, the communication interface is set to SPI.

The SCLK pin (Pin 25) is used to determine whether the communication method is I2C or UART. If this pin is held high, the communication interface is set to I2C; if it is held low, the communication interface is set to UART.

•

Table 9. Communication Autodetection

Communication Interface Pin 28 (CS) Pin 25 (SCLK) Pin 27 (MOSI/SCL/Rx) Pin 26 (MISO/SDA/Tx) SPI 0 Don’t care MOSI MISO 2

IC 1 1 SCL SDA UART 1 0 Rx Tx

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The most significant bit of this byte should be set to 1 for a read operation and to 0 for a write operation. When the third byte transmission is complete, the register data is either sent from the ADE7953 on the MISO pin (in the case of a read) or is written to the ADE7953 MOSI pin by the external microcontroller (in the case of a write). All data is sent or received MSB first. The length of the data transfer depends on the width of the register being accessed. Registers can be 8, 16, 24, or 32 bits long. Figure 68 and Figure 69 show the data transfer sequence for an SPI read and an SPI write, respectively. As shown in these figures, the CS (chip select) input must be driven low to initialize the communication and driven high at the end of the communi-cation. Bringing the CS input high before the completion of a data transfer ends the communication. In this way, the CS input performs a reset function on the SPI communication. The CS input allows communication with multiple devices on the same microcontroller SPI port.

SPI INTERFACE

The serial peripheral interface (SPI) uses all four communica-tion pins: CS, SCLK, MOSI, and MISO. The SPI communication operates in slave mode and, therefore, a clock must be provided on the SCLK pin (MOSI is an input, and MISO is an output). This clock synchronizes all communications and can operate up to a maximum speed of 5 MHz. See the SPI Interface Timing section for more information about the communication timing requirements.

The MOSI pin is an input to the ADE7953; data is shifted in on the falling edge of SCLK to be sampled by the ADE7953 on the rising edge. The MISO pin is an output from the ADE7953; data is shifted out on the falling edge of SCLK and should be sampled by the external microcontroller on the rising edge.

The SPI communication packet consists of two initial bytes that contain the address of the register that is to be read from or written to. This address should be transmitted MSB first. The third byte of the communication determines whether a read or a write is being issued.

CSSCLK1514MOSI10100000003130MISO1009320-06209320-063REGISTERADDRESSREGISTERVALUE

Figure 68. SPI Read

CSSCLK15141000000000313010MOSIREGISTERADDRESSREGISTERVALUE

Figure 69. SPI Write

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I2C Write Operations

A write operation on the ADE7953 is initiated when the master issues a start condition, which consists of the slave address and the read/write bit. The start condition is followed by the 16-bit address of the target register. After each byte is received, the ADE7953 issues an acknowledge (ACK) to the master. As soon as the 16-bit address communication is complete, the master sends the register data, MSB first. The length of this data can be 8, 16, 24, or 32 bits long. After each byte of register data is received, the ADE7953 slave issues an acknowledge (ACK). When transmission of the final byte is complete, the master issues a stop condition, and the bus returns to the idle condition. The I2C write operation is shown in Figure 70.

I2C INTERFACE

The ADE7953 supports a fully licensed I2C interface. The I2C interface operates as a slave and uses two shared pins: SDA and SCL. The SDA pin is a bidirectional input/output pin, and the SCL pin is the serial clock. Both pins are shared with the SPI and UART interfaces. The I2C interface operates at a maximum serial clock frequency of 400 kHz.

The two pins used for data transfer—SDA and SCL—are configured in a wire-AND format that allows arbitration in a multimaster system.

Communication via the I2C interface is initiated by the master device generating a start condition. This consists of the master transmitting a single byte containing the address of the slave device and the nature of the operation (read or write).

The address of the ADE7953 is 0111000X. Bit 7 in the address byte indicates whether a read or a write is required: 0 indicates a write, and 1 indicates a read. The communication continues as described in the following sections until the master issues a stop condition and the bus returns to the idle condition.

START1587023161587070S01110000READ/WRITESLAVEADDRESSACKMSB OF REGISTERADDRESSACKLSB OF REGISTERADDRESSACKBYTE 3 (MSB) OF REGISTERACKBYTE 2 OF REGISTERACKBYTE 1 OF REGISTERACKBYTE 0 (LSB) OF REGISTERACK09320-059ACK GENERATED BYADE7953STOPP

Figure 70. IC Write

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The second stage of the read operation begins with the master generating a new start condition. This start condition consists of the same slave address but with the LSB set to 1 to signify that a read is being issued. After this byte is received, the ADE7953 issues an acknowledge (ACK). The ADE7953 then sends the register contents to the master, which acknowledges the reception of each byte. All bytes are sent MSB first. The register contents can be 8, 16, 24, or 32 bits long. After the final byte of register data is received, the master issues a stop condition in place of the acknowledge to indicate the completion of the communication. The I2C read operation is shown in Figure 71.

I2C Read Operations

The I2C read operation is performed in two stages. The first stage sets the pointer to the address of the register to be accessed. The second stage reads the contents of the register. As shown in Figure 71, the first stage is initiated when the master issues a start condition, which consists of the slave

address and the read/write bit. Because this first step sets up the pointer to the address, the LSB of the start byte should be set to 0 (write). The start condition is followed by the 16-bit address of the target register. After each byte is received, the ADE7953 issues an acknowledge (ACK) to the master.

START1501110000READ/WRITE870SSLAVEADDRESSAAACMSB OF REGISTERADDRESSCLSB OF REGISTERADDRESSCKKKACK GENERATED BYADE7953ACK GENERATED BYMASTERSTARTSTOPPACK09320-0602301110001READ/WRITE16AC15K8ACK70ACK70SSLAVEADDRESSBYTE 3 (MSB)OF REGISTERBYTE 2 OF REGISTERBYTE 1 OF REGISTERBYTE 0 (LSB)OF REGISTERACK GENERATED BYADE7953

Figure 71. IC Read

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Table 10. Frames in the UART Packet

Frame Function F1 Read/write F2 Address MSB F3 Address LSB

UART INTERFACE

The ADE7953 provides a simple universal asynchronous

receiver/transmitter (UART) interface that allows all the functions of the ADE7953 to be accessed using only two single-direction pins. The UART interface allows an isolated communication interface to be achieved using only two low cost opto-isolators. The UART interface operates at a fixed baud rate of 4800 bps and is therefore suitable for low speed designs.

The UART interface on the ADE7953 is accessed via the Tx pin (Pin 26), which transmits data from the ADE7953, and the Rx pin (Pin 27), which receives data from the microcontroller. A simple master/slave topology is implemented on the UART inter-face with the ADE7953 acting as the slave. All communication is initiated by the sending of a valid frame by the master (the microcontroller) to the slave (the ADE7953). The format of the frame is shown in Figure 72.

As shown in Figure 72, each frame consists of 10 bits. Each bit is sent at a bit rate of 4800 bps, resulting in a frame time of 2.08 ms ((1/4800) × 10). A wait period of 6 ms should be added from when the UART communication mode is established using the CS and SCLK pins to when the first frame is sent. A minimum wait of 0.2 ms should be included between frames. All frame data is sent LSB first.

Communication via the UART interface is initiated by the master sending a packet of three frames (see Table 10).

t2SCLKCSF1 determines whether the communication is a read or a write operation, and the following two frames (F2 and F3) select the register that is to be accessed. Each frame consists of eight data bits, as shown in Figure 72. A read is issued by writing the value 0x35 to F1, and a write is issued by writing the value 0xCA to F1. Any other value is interpreted as invalid and results in an unsuccessful communication with the ADE7953. The address bytes are sent MSB first; therefore, F2 contains the most significant portion of the address, and F3 contains the least significant portion of the address. The bits within each address frame are sent LSB first.

The ADE7953 UART interface uses two timeouts, t1 and t2, to synchronize the communication and to prevent the communi-cation from halting. The first timeout, t1, is the frame-to-frame delay and is fixed at 4 ms max. The second timeout, t2, is the packet-to-packet delay and is fixed at 6 ms min. These two timeouts act as a reset for the UART function. More informa-tion about how the timeouts are implemented is provided in the UART Read section and the UART Write section. Verification of a successful UART communication can be achieved by implementing a write/read/verify sequence in the microcontroller. Successful communications are also recorded in the LAST_ADD, LAST_RWDATA, and LAST_OP registers, as described in the Communication Verification section.

t1STARTD4D5D6D0D1D2D3D7D009320-141RxFRAMEt1 = FRAME DELAY: 0.2ms (MIN), 4ms (MAX)t2 =PACKET DELAY: 6ms (MIN)STARTSTOP

Figure 72. UART Frame

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UART Write

A write to the ADE7953 via the UART interface is initiated by the master sending a packet of three frames. If the first frame has the value 0xCA, a write is being issued. The second and third frames contain the address of the register being accessed. The next two frames contain the data to be written. When the ADE7953 receives a legal packet, it decodes the command as follows: •

If the number of frames obtained after the initial packet is the same as the size of the register specified by F2 and F3, the packet is legal and the corresponding register is written. If the number of frames does not equal the size of the specified register, the command is illegal and no further action is taken.

UART Read

A read from the ADE7953 via the UART interface is initiated by the master sending a packet of three frames. If the first frame has the value 0x35, a read is being issued. The second and third frames contain the address of the register being accessed. When the ADE7953 receives a legal packet, it decodes the command (see Figure 73).

The frame time is 2.08 ms. A frame-to-frame delay (t1) of 4 ms max provides a 50% buffer on the frame time without needlessly slowing the communication. When the read packet is decoded, the ADE7953 sends the data from the selected register out on the Tx pin (see F4 and F5 in Figure 73). This occurs approximately 0.1 ms after the complete frame is received. This data can be 1, 2, 3, or 4 bytes long, depending on the size of the register that is being accessed. The register data is sent LSB first. After the last frame of register data is sent from the ADE7953, a packet-to-packet delay (t2) of 6 ms min is required before any incoming data on the Rx pin is accepted. This packet-to-packet timeout ensures that no overlap is possible.

t1RxF1READ/WRITEF2ADDRESSMSB•

After the last frame of data is received on the Rx pin, a wait period of t2 is required before any incoming data on the Rx pin is treated as a new packet. This operation is shown in Figure 74.

t1F3ADDRESSLSBF1READ/WRITEt1F2ADDRESSMSBt1TxF4DATALSBt1F5DATAMSBt209320-142

Figure 73. UART Read

t1RxF1READ/WRITEF2ADDRESSMSBt1F3ADDRESSLSBt1F4DATALSBt1F5DATAMSBF1READ/WRITEt1F2ADDRESSMSBt2Tx09320-143

Figure 74. UART Write

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COMMUNICATION VERIFICATION

The ADE7953 includes a set of three registers that allow any communication via SPI, I2C, or UART to be verified. The LAST_OP (Address 0x0FD), LAST_ADD (Address 0x1FE), and LAST_RWDATA registers record the type, address, and data of the last successful communication, respectively. The LAST_RWDATA register has four separate addresses, depending on the length of the successful communication (see Table 11). Multiple address locations are included to prevent unnecessarily long communications.

Table 11. Addresses of the LAST_RWDATA Registers

COMMUNICATION VERIFICATION AND SECURITY

The ADE7953 includes three security measures to increase communication robustness and to help prevent inadvertent modifications to its internal registers. The write protection, communication verification, and checksum features can be used together to help increase the robustness and noise immunity of the meter design.

WRITE PROTECTION

The ADE7953 provides a simple method for protecting the internal registers from unexpected write operations. This feature helps to prevent noise or EMC conditions from changing the required meter configuration. The write protection feature is disabled by default to allow the meter to be configured and can be enabled by writing to the 8-bit WRITE_PROTECT register (Address 0x040). Only the three LSBs of this register are used. Bit 0 controls the protection on the 8-bit registers; Bit 1 controls the protection on the 16-bit registers; Bit 2 controls the protection on the 24-/32-bit registers. All bits are set to 0 by default to dis-able the protection. Setting any of these bits to 1 enables write protection on the corresponding group of registers. When write protection is enabled, any attempted write operation using the SPI, I2C, or UART interface is ignored. Resetting the WRITE_ PROTECT bits to 0 reinstates full access to the register banks.

Length of Read/Write 8 bits 16 bits 24 bits 32 bits

After each successful communication with the ADE7953, the address of the last register that was accessed is stored in the 16-bit LAST_ADD register (Address 0x1FE). This read-only register stores the value until the next successful read or write is complete.

The LAST_OP register (Address 0x0FD) stores the type of the communication, that is, it indicates whether a read or a write was performed. If the last operation was a write, the LAST_OP register stores the value 0xCA. If the last operation was a read, the LAST_OP register stores the value 0x35.

The LAST_RWDATA register stores the data that was written to or read from the register. Unsuccessful read and write operations are not reflected in these registers.

Rev. 0 | Page 56 of 68

ADE7953

CHECKSUM REGISTER

The checksum can be used to ensure that the registers included in the checksum are not inadvertently changed by periodically The ADE7953 includes a 32-bit checksum register, CRC

reading the value in the CRC register (Address 0x37F) after the (Address 0x37F), which warns the user if any of the important

meter is configured. If two consecutive readings differ, it can be configuration, control, or calibration registers are modified. The

assumed that one of the registers has changed value and, therefore, checksum register helps to ensure that the meter configuration

the configuration of the ADE7953 has changed. The recommended is not modified from its desired state during normal operation.

response is to issue a hardware/software reset, which resets all GTable 12 lists the registers included in the checksum. GADE7953 registers, including reserved registers, to their default

An additional six internal reserved registers are also included in values. The ADE7953 should then be reconfigured with the the checksum. The ADE7953 computes the cyclic redundancy design-specific settings. check (CRC) based on the IEEE 802.3 standard. The contents of

An interrupt associated with the checksum feature can provide the registers are introduced one by one into a linear feedback

an external warning signal on the IRQ pin if the CRC register shift register (LFSR) based generator, starting with the least

value changes after initial configuration. This interrupt is dis-significant bit. The 32-bit result is written to the CRC register.

abled by default and can be enabled by setting the CRC bit (Bit 21) The CRC is disabled by default and can be enabled by setting

in the IRQENA register (Address 0x22C and Address 0x32C). the CRC_ENABLE bit (Bit 8) of the CONFIG register (Address

When this interrupt is enabled, an external interrupt is issued 0x102). When this bit is set, the CRC is computed. Because the

if the CRC value changes from the value that it held at the time CRC is disabled by default, the default value is 0xFFFFFFFF.

that it was enabled.

Table 12. Registers Included in the Checksum

Configuration and Control Registers Calibration Registers

Register Name Address Register Name Address LCYCMODE 0x004 AIGAIN 0x280 and 0x380 PGA_V 0x007 VGAIN 0x281 and 0x381 PGA_IA 0x008 AWGAIN 0x282 and 0x382 PGA_IB 0x009 AVARGAIN 0x283 and 0x383 CONFIG 0x102 AVAGAIN 0x284 and 0x384 CF1DEN 0x103 AIOS 0x285 and 0x385 CF2DEN 0x104 AIRMSOS 0x286 and 0x386 CFMODE 0x107 VOS 0x287 and 0x387 PHCALA 0x108 VRMSOS 0x288 and 0x388 PHCALB 0x109 AWATTOS 0x289 and 0x389 ALT_OUTPUT 0x110 AVAROS 0x28A and 0x38A ACCMODE 0x201 and 0x301 AVAOS 0x28B and 0x38B IRQENA 0x22C and 0x32C BIGAIN 0x28C and 0x38C IRQENB 0x22F and 0x32F BWGAIN 0x28E and 0x38E BVARAIN 0x28F and 0x38F BVAAIN 0x290 and 0x390 BIOS 0x291 and 0x391 BIRMSOS 0x292 and 0x392 BWATTOS 0x295 and 0x395 BVAROS 0x296 and 0x396 BVAOS 0x297 and 0x397

Rev. 0 | Page 57 of 68

ADE7953

ADE7953 REGISTERS

The ADE7953 contains registers that are 8, 16, 24, and 32 bits long. All signed registers are in the twos complement format with the

Gexception of the PHCALA and PHCALB registers, which are in sign magnitude format. The 24-bit and 32-bit registers contain the same

data but can be accessed in two different register lengths. The 24-bit register option increases communication speed; the 32-bit register G

option provides simplicity when coding with the long format. When accessing the 32-bit registers, only the lower 24 bits contain valid data (the upper 8 bits are sign extended). A write to a 24-bit register changes the value in the corresponding 32-bit register, and vice versa. Therefore, each 24-/32-bit register can be thought of as one memory location that can be accessed via two different paths. Table 13. 8-Bit Registers

Address Register Name

G0x000 SAGCYC

0x001 DISNOLOAD 0x004 LCYCMODE 0x007 PGA_V

0x008 PA_IA 0x009 PA_IB

0x040 WRITE_PROTECT 0x0FD LAST_OP R/W R/W

R/W R/W R/W

R/W R/W R/W R

Default 0x00

0x00 0x40 0x00

0x00 0x00 0x00 0x00

Type Register Description Unsigned Sag line cycles Unsigned No-load detection disable Unsigned Line cycle accumulation mode configuration Unsigned Voltage channel gain configuration (Bits[2:0]) Unsigned Current Channel A gain configuration (Bits[2:0]) Unsigned Current Channel B gain configuration (Bits[2:0]) Unsigned Write protection bits (Bits[2:0]) Unsigned Contains the type (read or write) of the last successful

communication (0x35 = read; 0xCA = write)

0x00 Unsigned Contains the data from the last successful 8-bit register

communication

N/A Unsigned Contains the silicon version number 0x00 Unsigned Reference input configuration: set to 0 for internal; set

to 1 for external

0x0FF LAST_RWDATA R G0x702 GVersion

0x800 EX_REF R

R/W

Table 14. 16-Bit Registers

Address Register Name 0x100 ZXTOUT 0x101 LINECYC 0x102 CONFI 0x103 CF1DEN 0x104 CF2DEN 0x107 CFMODE 0x108 PHCALA 0x109 PHCALB 0x10A PFA 0x10B PFB

0x10C ANLE_A 0x10D ANLE_B 0x10E Period 0x110 ALT_OUTPUT

0x1FE LAST_ADD 0x1FF LAST_RWDATA R/W

R/W R/W R/W R/W R/W R/W R/W R/W R R

R R R R/W R R

Default Type Register Description 0xFFFF Unsigned Zero-crossing timeout 0x0000 Unsigned Number of half line cycles for line cycle energy

accumulation mode

0x8004 Unsigned Configuration register 0x003F Unsigned CF1 frequency divider denominator 0x003F Unsigned CF2 frequency divider denominator 0x0300 Unsigned CF output selection

0x0000 Signed Phase calibration register (Current Channel A). This register is in sign magnitude format.

0x0000 Signed Phase calibration register (Current Channel B). This register is in sign magnitude format.

0x0000 Signed Power factor (Current Channel A) 0x0000 Signed Power factor (Current Channel B)

0x0000 Signed Angle between the voltage input and the Current Channel A input

0x0000 Signed Angle between the voltage input and the Current

Channel B input

0x0000 Unsigned Period register 0x0000 Unsigned Alternative output functions 0x0000 Unsigned Contains the address of the last successful

communication

0x0000 Unsigned Contains the data from the last successful 16-bit

Rev. 0 | Page 58 of 68

ADE7953

Table 15. 24-/32-Bit Registers

Address

G24-Bit 32-Bit Register Name G0x200 0x300 SAGLVL

G0x201 0x301 ACCMODE 0x203 0x303 AP_NOLOAD 0x204 0x304 VAR_NOLOAD 0x205 0x305 VA_NOLOAD 0x210 0x310 AVA 0x211 0x311 BVA 0x212 0x312 AWATT 0x213 0x313 BWATT 0x214 0x314 AVAR 0x215 0x315 BVAR 0x216 0x316 IA 0x217 0x317 IB 0x218 0x318 V 0x21A 0x31A IRMSA 0x21B 0x31B IRMSB 0x21C 0x31C VRMS 0x21E 0x31E AENERGYA 0x21F 0x31F AENERGYB 0x220 0x320 RENERGYA 0x221 0x321 RENERGYB 0x222 0x322 APENERGYA 0x223 0x323 APENERGYB 0x224 0x324 OVLVL 0x225 0x325 OILVL 0x226 0x326 VPEAK 0x227 0x327 RSTVPEAK 0x228 0x328 IAPEAK

0x229 0x329 RSTIAPEAK 0x22A 0x32A IBPEAK

0x22B 0x32B RSTIBPEAK 0x22C 0x32C IRQENA 0x22D 0x32D IRQSTATA 0x22E 0x32E RSTIRQSTATA 0x22F 0x32F IRQENB 0x230 0x330 IRQSTATB 0x231 0x331 RSTIRQSTATB N/A 0x37F CRC 0x280 0x380 AIAIN 0x281 0x381 VGAIN

0x282 0x382 AWAIN 0x283 0x383 AVARAIN 0x284 0x384 AVAGAIN 0x285 0x385 AIOS 0x286 0x386 AIRMSOS 0x287 0x387 VOS

0x288 0x388 VRMSOS 0x289 0x389 AWATTOS 0x28A 0x38A AVAROS 0x28B 0x38B AVAOS R/W Default Type Register Description R/W 0x000000 Unsigned Sag voltage level R/W 0x000000 Unsigned Accumulation mode R/W 0x00E419 Unsigned Active power no-load level R/W 0x00E419 Unsigned Reactive power no-load level R/W 0x000000 Unsigned Apparent power no-load level R 0x000000 Signed Instantaneous apparent power (Current Channel A) R 0x000000 Signed Instantaneous apparent power (Current Channel B) R 0x000000 Signed Instantaneous active power (Current Channel A) R 0x000000 Signed Instantaneous active power (Current Channel B) R 0x000000 Signed Instantaneous reactive power (Current Channel A) R 0x000000 Signed Instantaneous reactive power (Current Channel B) R 0x000000 Signed Instantaneous current (Current Channel A) R 0x000000 Signed Instantaneous current (Current Channel B) R 0x000000 Signed Instantaneous voltage (voltage channel) R 0x000000 Unsigned IRMS register (Current Channel A) R 0x000000 Unsigned IRMS register (Current Channel B) R 0x000000 Unsigned VRMS register R 0x000000 Signed Active energy (Current Channel A) R 0x000000 Signed Active energy (Current Channel B) R 0x000000 Signed Reactive energy (Current Channel A) R 0x000000 Signed Reactive energy (Current Channel B) R 0x000000 Signed Apparent energy (Current Channel A) R 0x000000 Signed Apparent energy (Current Channel B) R/W 0xFFFFFF Unsigned Overvoltage level R/W 0xFFFFFF Unsigned Overcurrent level R 0x000000 Unsigned Voltage channel peak R 0x000000 Unsigned Read voltage peak with reset R 0x000000 Unsigned Current Channel A peak R 0x000000 Unsigned Read Current Channel A peak with reset R 0x000000 Unsigned Current Channel B peak R 0x000000 Unsigned Read Current Channel B peak with reset R/W 0x100000 Unsigned Interrupt enable (Current Channel A) R 0x000000 Unsigned Interrupt status (Current Channel A) R 0x000000 Unsigned Reset interrupt status (Current Channel A) R/W 0x000000 Unsigned Interrupt enable (Current Channel B) R 0x000000 Unsigned Interrupt status (Current Channel B) R 0x000000 Unsigned Reset interrupt status (Current Channel B) R 0xFFFFFFFF Unsigned Checksum R/W 0x400000 Unsigned Current channel gain (Current Channel A) R/W 0x400000 Unsigned Voltage channel gain R/W 0x400000 Unsigned Active power gain (Current Channel A) R/W 0x400000 Unsigned Reactive power gain (Current Channel A) R/W 0x400000 Unsigned Apparent power gain (Current Channel A) R/W 0x000000 Signed Current channel offset (Current Channel A) R/W 0x000000 Signed IRMS offset (Current Channel A) R/W 0x000000 Signed Voltage channel offset R/W 0x000000 Signed VRMS offset R/W 0x000000 Signed Active power offset correction (Current Channel A) R/W 0x000000 Signed Reactive power offset correction (Current Channel A) R/W 0x000000 Signed Apparent power offset correction (Current Channel A)

Rev. 0 | Page 59 of 68

ADE7953

R/W Default Type Register Description

R/W 0x400000 Unsigned Current channel gain (Current Channel B) R/W 0x400000 Unsigned Active power gain (Current Channel B) R/W 0x400000 Unsigned Reactive power gain (Current Channel B) R/W 0x400000 Unsigned Apparent power gain (Current Channel B) R/W 0x000000 Signed Current channel offset (Current Channel B) R/W 0x000000 Signed IRMS offset (Current Channel B) R/W 0x000000 Signed Active power offset correction (Current Channel B) R/W 0x000000 Signed Reactive power offset correction (Current Channel B) R/W 0x000000 Signed Apparent power offset correction (Current Channel B) R 0x000000 Unsigned Contains the data from the last successful 24-/32-bit

Address

24-Bit 32-Bit Register Name 0x28C 0x38C BIAIN 0x28E 0x38E BWAIN 0x28F 0x38F BVARAIN 0x290 0x390 BVAAIN 0x291 0x391 BIOS

0x292 0x392 BIRMSOS 0x295 0x395 BWATTOS 0x296 0x396 BVAROS 0x297 0x397 BVAOS 0x2FF 0x3FF LAST_RWDATA

ADE7953 REGISTER DESCRIPTIONS

Table 16. DISNOLOAD Register (Address 0x001)

Bits Bit Name 0 DIS_APNLOAD 1 DIS_VARNLOAD 2 DIS_VANLOAD

Bits Bit Name 0 ALWATT Default Description 0 1 = disable the active power no-load feature on Current Channel A and Current Channel B 0 1 = disable the reactive power no-load feature on Current Channel A and Current Channel B 0 1 = disable the apparent power no-load feature on Current Channel A and Current Channel B

Table 17. LCYCMODE Register (Address 0x004)

Default Description

0 0 = disable active energy line cycle accumulation mode on Current Channel A

1 = enable active energy line cycle accumulation mode on Current Channel A

1 BLWATT 0 0 = disable active energy line cycle accumulation mode on Current Channel B

G1 = enable active energy line cycle accumulation mode on Current Channel B G2 ALVAR 0 0 = disable reactive energy line cycle accumulation mode on Current Channel A G

1 = enable reactive energy line cycle accumulation mode on Current Channel A G

3 BLVAR 0 0 = disable reactive energy line cycle accumulation mode on Current Channel B

1 = enable reactive energy line cycle accumulation mode on Current Channel B

4 ALVA 0 0 = disable apparent energy line cycle accumulation mode on Current Channel A

1 = enable apparent energy line cycle accumulation mode on Current Channel A

5 BLVA 0 0 = disable apparent energy line cycle accumulation mode on Current Channel B

1 = enable apparent energy line cycle accumulation mode on Current Channel B

6 RSTREAD 1 0 = disable read with reset for all registers

1 = enable read with reset for all registers

Table 18. CONFIG Register (Address 0x102) Bits Bit Name 0 INTENA 1 INTENB 2 HPFEN 3 PFMODE Default Description 0 1 = integrator enable (Current Channel A) 0 1 = integrator enable (Current Channel B) 1 1 = HPF enable (all channels) 0 0 = power factor is based on instantaneous powers 1 = power factor is based on line cycle accumulation mode energies 4 REVP_CF 0 0 = REVP is updated on CF1 1 = REVP is updated on CF2 5 REVP_PULSE 0 0 = REVP is high when reverse polarity is true, low when reverse polarity is false 1 = REVP outputs a 1 Hz pulse when reverse polarity is true and is low when reverse polarity is false 6 ZXLPF 7 SWRST 0 0 = ZX LPF is enabled 1 = ZX LPF is disabled 0 Setting this bit enables a software reset Rev. 0 | Page 60 of 68

ADE7953

Bits Bit Name Default Description 8 CRC_ENABLE 0 0 = CRC is disabled

1 = CRC is enabled

[10:9] PWR_LPF_SEL 00 Low-pass filter options Setting Filtering 00 ~250 ms

01 ~500 ms 10 ~1 sec

11 ~2 sec 11 ZX_I 0 0 = ZX_I is based on Current Channel A

1 = ZX_I is based on Current Channel B

[13:12] ZX_EDGE 00 Zero-crossing interrupt edge selection Setting Edge Selection 00 Interrupt is issued on both positive-going and negative-going zero crossing

01 Interrupt is issued on negative-going zero crossing 10 Interrupt is issued on positive-going zero crossing 11 Interrupt is issued on both positive-going and negative-going zero crossing

14 Reserved 0 Reserved 15 COMM_LOCK 1 0 = communication locking feature is enabled

1 = communication locking feature is disabled

Table 19. CFMODE Register (Address 0x107)

Bits Bit Name [3:0] CF1SEL

Default Description

0000 Configuration of output signal on CF1 pin Setting CF1 Output Signal Configuration 0000 CF1 is proportional to active power (Current Channel A)

0001 CF1 is proportional to reactive power (Current Channel A) 0010 CF1 is proportional to apparent power (Current Channel A)

0011 CF1 is proportional to IRMS (Current Channel A) 0100 CF1 is proportional to active power (Current Channel B)

0101 CF1 is proportional to reactive power (Current Channel B) 0110 CF1 is proportional to apparent power (Current Channel B)

0111 CF1 is proportional to IRMS (Current Channel B) 1000 CF1 is proportional to IRMS (Current Channel A) + IRMS (Current Channel B) 1001 CF1 is proportional to active power (Current Channel A) + active power

(Current Channel B)

0000 Configuration of output signal on CF2 pin Setting CF2 Output Signal Configuration 0000 CF2 is proportional to active power (Current Channel A)

0001 CF2 is proportional to reactive power (Current Channel A) 0010 CF2 is proportional to apparent power (Current Channel A)

0011 CF2 is proportional to IRMS (Current Channel A) 0100 CF2 is proportional to active power (Current Channel B)

0101 CF2 is proportional to reactive power (Current Channel B) 0110 CF2 is proportional to apparent power (Current Channel B)

0111 CF2 is proportional to IRMS (Current Channel B) 1000 CF2 is proportional to IRMS (Current Channel A) + IRMS (Current Channel B) 1001 CF2 is proportional to active power (Current Channel A) + active power

(Current Channel B)

1 0 = CF1 output is enabled

1 = CF1 output is disabled

1 0 = CF2 output is enabled

1 = CF2 output is disabled

Rev. 0 | Page 61 of 68

[7:4]

CF2SEL

8 CF1DIS 9 CF2DIS ADE7953

Default Description 0000 Configuration of ZX pin (Pin 1) Setting ZX Pin Configuration 0000 ZX detection is output on Pin 1 (default) 0001 Sag detection is output on Pin 1 0010 Reserved 0011 Reserved 0100 Reserved 0101 Active power no-load detection (Current Channel A) is output on Pin 1 0110 Active power no-load detection (Current Channel B) is output on Pin 1 0111 Reactive power no-load detection (Current Channel A) is output on Pin 1 1000 Reactive power no-load detection (Current Channel B) is output on Pin 1 1001 Unlatched waveform sampling signal is output on Pin 1 1010 IRQ signal is output on Pin 1 1011 ZX_I detection is output on Pin 1 1100 REVP detection is output on Pin 1 1101 Reserved (set to default value) 111x Reserved (set to default value) 0000 Configuration of ZX_I pin (Pin 21) Setting ZX_I Pin Configuration 0000 ZX_I detection is output on Pin 21 (default) 0001 Sag detection is output on Pin 21 0010 Reserved 0011 Reserved 0100 Reserved 0101 Active power no-load detection (Current Channel A) is output on Pin 21 0110 Active power no-load detection (Current Channel B) is output on Pin 21 0111 Reactive power no-load detection (Current Channel A) is output on Pin 21 1000 Reactive power no-load detection (Current Channel B) is output on Pin 21 1001 Unlatched waveform sampling signal is output on Pin 21 1010 IRQ signal is output on Pin 21 1011 ZX detection is output on Pin 21 1100 REVP detection is output on Pin 21 1101 Reserved (set to default value) 111x Reserved (set to default value) 0000 Configuration of REVP pin (Pin 20) REVP Pin Configuration Setting 0000 REVP detection is output on Pin 20 (default) 0001 Sag detection is output on Pin 20 0010 Reserved 0011 Reserved 0100 Reserved 0101 Active power no-load detection (Current Channel A) is output on Pin 20 0110 Active power no-load detection (Current Channel B) is output on Pin 20 0111 Reactive power no-load detection (Current Channel A) is output on Pin 20 1000 Reactive power no-load detection (Current Channel B) is output on Pin 20 1001 Unlatched waveform sampling signal is output on Pin 20 1010 IRQ signal is output on Pin 20 1011 ZX detection is output on Pin 20 1100 ZX_I detection is output on Pin 20 1101 Reserved (set to default value) 111x Reserved (set to default value) Rev. 0 | Page 62 of 68

Table 20. ALT_OUTPUT Register (Address 0x110) Bits Bit Name [3:0] ZX_ALT [7:4] ZXI_ALT [11:8] REVP_ALT

ADE7953

Table 21. ACCMODE Register (Address 0x201 and Address 0x301)

Bits Bit Name [1:0] AWATTACC

Default Description 00 Current Channel A active energy accumulation mode Setting Active Energy Accumulation Mode (Current Channel A) 00 Normal mode

01 Positive-only accumulation mode 10 Absolute accumulation mode

11 Reserved G[3:2] BWATTACC 00 Current Channel B active energy accumulation mode G Setting Active Energy Accumulation Mode (Current Channel B)

00 Normal mode

G01 Positive-only accumulation mode

10 Absolute accumulation mode 11 Reserved [5:4] AVARACC 00 Current Channel A reactive energy accumulation mode Setting Reactive Energy Accumulation Mode (Current Channel A) 00 Normal mode

01 Antitamper accumulation mode 10 Absolute accumulation mode

11 Reserved [7:6] BVARACC 00 Current Channel B reactive energy accumulation mode Setting Reactive Energy Accumulation Mode (Current Channel B) 00 Normal mode

01 Antitamper accumulation mode 10 Absolute accumulation mode

11 Reserved

8 AVAACC 0 0 = Current Channel A apparent energy accumulation is in normal mode

1 = Current Channel A apparent energy accumulation is based on IRMSA

9 BVAACC 0 0 = Current Channel B apparent energy accumulation is in normal mode

1 = Current Channel B apparent energy accumulation is based on IRMSB

10 APSIN_A 0 0 = active power on Current Channel A is positive

1 = active power on Current Channel A is negative

11 APSIN_B 0 0 = active power on Current Channel B is positive

1 = active power on Current Channel B is negative

12 VARSIN_A 0 0 = reactive power on Current Channel A is positive

1 = reactive power on Current Channel A is negative

13 VARSIN_B 0 0 = reactive power on Current Channel B is positive

1 = reactive power on Current Channel B is negative

[15:14] Reserved 00 Reserved 16 ACTNLOAD_A 0 0 = Current Channel A active energy is out of no-load condition

1 = Current Channel A active energy is in no-load condition

17 VANLOAD_A 0 0 = Current Channel A apparent energy is out of no-load condition

1 = Current Channel A apparent energy is in no-load condition

18 VARNLOAD_A 0 0 = Current Channel A reactive energy is out of no-load condition

1 = Current Channel A reactive energy is in no-load condition

19 ACTNLOAD_B 0 0 = Current Channel B active energy is out of no-load condition

1 = Current Channel B active energy is in no-load condition

20 VANLOAD_B 0 0 = Current Channel B apparent energy is out of no-load condition

1 = Current Channel B apparent energy is in no-load condition

21 VARNLOAD_B 0 0 = Current Channel B reactive energy is out of no-load condition

1 = Current Channel B reactive energy is in no-load condition

Rev. 0 | Page 63 of 68

ADE7953

Interrupt Enable and Interrupt Status Registers Current Channel A and Voltage Channel Registers

Table 22. IRQENA Register (Address 0x22C and Address 0x32C), IRQSTATA Register (Address 0x22D and Address 0x32D), and RSTIRQSTATA Register (Address 0x22E and Address 0x32E)

Bits Bit Name 0 AEHFA 1 VAREHFA 2 VAEHFA 3 AEOFA 4 VAREOFA 5 VAEOFA 6 AP_NOLOADA 7 VAR_NOLOADA 8 VA_NOLOADA 9 APSIGN_A 10 VARSIGN_A

11 ZXTO_IA 12 ZXIA 13 OIA

14 ZXTO 15 16 17 18 19 20 21

ZXV OV WSMP CYCEND Sag Reset CRC

Description

Active energy is half full (Current Channel A) Reactive energy is half full (Current Channel A) Apparent energy is half full (Current Channel A)

Active energy has overflowed or underflowed (Current Channel A) Reactive energy has overflowed or underflowed (Current Channel A) Apparent energy has overflowed or underflowed (Current Channel A) Active power no-load detection on Current Channel A Reactive power no-load detection on Current Channel A Apparent power no-load detection on Current Channel A Sign of active energy has changed (Current Channel A) Sign of reactive energy has changed (Current Channel A)

Indicates that a zero crossing has been missing on Current Channel A for the length of time specified in the ZXTOUT register

Current Channel A zero crossing

Current Channel A peak has exceeded the overcurrent threshold set in the OILVL register

Indicates that a zero crossing has been missing on the voltage channel for the length of time specified in the ZXTOUT register

Voltage channel zero crossing

Voltage peak has exceeded the overvoltage threshold set in the OVLVL register New waveform data acquired

End of a line cycle accumulation period Sag event has occurred

End of a software or hardware reset Checksum has changed

Current Channel B Registers

Table 23. IRQENB Register (Address 0x22F and Address 0x32F), IRQSTATB Register (Address 0x230 and Address 0x330), and RSTIRQSTATB Register (Address 0x231 and Address 0x331)

Bits Bit Name 0 AEHFB 1 VAREHFB 2 VAEHFB 3 AEOFB 4 VAREOFB 5 VAEOFB 6 AP_NOLOADB 7 VAR_NOLOADB 8 VA_NOLOADB 9 APSIGN_B 10 VARSIGN_B

11 ZXTO_IB 12 13

ZXIB OIB

Description

Active energy is half full (Current Channel B) Reactive energy is half full (Current Channel B) Apparent energy is half full (Current Channel B)

Active energy has overflowed or underflowed (Current Channel B) Reactive energy has overflowed or underflowed (Current Channel B) Apparent energy has overflowed or underflowed (Current Channel B) Active power no-load detection on Current Channel B Reactive power no-load detection on Current Channel B Apparent power no-load detection on Current Channel B Sign of active energy has changed (Current Channel B) Sign of reactive energy has changed (Current Channel B)

Indicates that a zero crossing has been missing on Current Channel B for the length of time specified in the ZXTOUT register

Current Channel B zero crossing

Current Channel B peak has exceeded the overcurrent threshold set in the OILVL register

Rev. 0 | Page 64 of 68

ADE7953

OUTLINE DIMENSIONS

PIN1INDICATOR5.105.00SQ4.900.50BSC0.300.250.202221281PIN1INDICATOREXPOSEDPAD3.403.30SQ3.20715TOPVIEW0.800.750.70SEATINGPLANE0.500.400.30148BOTTOMVIEWFORPROPERCONNECTIONOFTHEEXPOSEDPAD,REFERTOTHEPINCONFIGURATIONANDFUNCTIONDESCRIPTIONSSECTIONOFTHISDATASHEET.0.05MAX0.02NOMCOPLANARITY0.080.203REFCOMPLIANTTOJEDECSTANDARDSMO-220-WHHD-3.120909-A

Figure 75. 28-Lead Lead Frame Chip Scale Package [LFCSP_WQ]

5 mm × 5 mm Body, Very Very Thin Quad

(CP-28-6)

Dimensions shown in millimeters

ORDERING GUIDE

Model1Temperature Range ADE7953ACPZ −40°C to +85°C ADE7953ACPZ-RL −40°C to +85°C EVAL-ADE7953EBZ

Package Description 28-Lead LFCSP_WQ

28-Lead LFCSP_WQ, 13” Tape and Reel Evaluation Board Package Option

CP-28-6 CP-28-6

Z = RoHS Compliant Part.

Rev. 0 | Page 65 of 68

ADE7953

NOTES

Rev. 0 | Page 66 of 68

ADE7953

NOTES

Rev. 0 | Page 67 of 68

ADE7953

NOTES

I2C refers to a communications protocol originally developed by Philips Semiconductors (now NXP Semiconductors).

Rev. 0 | Page 68 of 68

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